LT6700/LT6700HV
13
6700123fh
For more information www.linear.com/LT6700
TYPICAL PERFORMANCE CHARACTERISTICS
Output Saturation Voltage
vs Output Sink Current
Output Saturation Voltage
vs Output Sink Current
Output Saturation Voltage
vs Output Sink Current
Output Short-Circuit Current
Output Short-Circuit Current
Output Leakage Current
Propagation Delay
vs Input Overdrive
Rise and Fall Times
vs Output Pull-Up Resistor
Noninverting and Inverting
Comparator Propagation Delay
OUTPUT SINK CURRENT (mA)
10
OUTPUT SATURATION VOLTAGE (mV)
100
0.001 0.1 1 10
6700123 G19
1
0.01
1000
100
T
A
= –40°C
V
S
= 1.4V
V
S
= 5V
V
S
= 12V
V
S
= 18V
OUTPUT SINK CURRENT (mA)
10
OUTPUT SATURATION VOLTAGE (mV)
100
0.001 0.1 1 10
6700123 G20
1
0.01
1000
100
T
A
= 25°C
V
S
= 1.4V
V
S
= 5V
V
S
= 12V
V
S
= 18V
OUTPUT SINK CURRENT (mA)
10
OUTPUT SATURATION VOLTAGE (mV)
100
0.001 0.1 1 10
6700123 G21
1
0.01
1000
100
T
A
= 85°C
V
S
= 1.4V
V
S
= 5V
V
S
= 12V
V
S
= 18V
OUTPUT VOLTAGE (V)
0
SHORT-CIRCUIT CURRENT (mA)
40
50
60
6700123 G22
30
20
2 4 1614 18
6
8 10 12
10
80
70
0
T
A
= 25°C
T
A
= 85°C
T
A
= 125°C
T
A
= –55°C
V
S
= 5V
OUTPUT VOLTAGE (V)
0
SHORT-CIRCUIT CURRENT (mA)
40
50
60
6700123 G23
30
20
2 4 1614 18
6
8 10 12
10
80
70
0
T
A
= 25°C
V
S
= 1.4V
V
S
= 5V
V
S
= 12V
V
S
= 18V
OUTPUT VOLTAGE (V)
0.01
OUTPUT LEAKAGE CURRENT (nA)
0.1
1
10
0 8 10 12 14 16
0.001
2 4 6
18
6700123 G24
T
A
= 25°C
T
A
= 85°C
T
A
= 125°C
T
A
= –55°C
V
S
= 5V
INPUT OVERDRIVE (mV)
0
PROPAGATION DELAY (µs)
30
40
50
60
80
6700123 G25
20
10
0
20
40
60
100
LH NONINV
HL NONINV
LH INV
HL INV
T
A
= 25°C
OUTPUT PULL-UP RESISTOR (kΩ)
0.1
0.01
RISE AND FALL TIME (µs)
1
100
1 10 100 1000
6700123 G26
0.1
10
V
S
= 5V
C
L
= 20pF
T
A
= 25°C
RISE
FALL
6700123 G27
V
O(NINV)
5V/DIV
DC
V
O(INV)
5V/DIV
DC
V
IN
10mV/DIV
AC
20µs/DIVV
S
= 15V
T
A
= 25°C
R
LOAD
= 10k CONNNECTED TO V
S
V
IN(OVERDRIVE)
= 10mV OVER THE INPUT
VOLTAGE THRESHOLDS
LT6700/LT6700HV
14
6700123fh
For more information www.linear.com/LT6700
APPLICATIONS INFORMATION
The LT6700-1/LT6700-2/LT6700-3/LT6700HV-1/
LT6700HV-2/LT6700HV-3 devices are a family of dual
micropower comparators with a built-in 400mV refer-
ence. Features include wide supply voltage range (1.4V to
18V), Over-The-Top input and output range, 2% accurate
rising input threshold voltage and 6.5mV typical built-in
hysteresis. The comparators open-collector outputs can
sink up to 40mA typical.
Internal Reference
Each of the comparator sections has one input available
externally, with the three versions of the part differing by
the polarity of those available inputs (i.e., inverting or
noninverting). The other comparator inputs are connected
internally to the 400mV reference. The rising input threshold
voltage of the comparators is designed to be equal to that
of the reference (i.e., ≈400mV). The reference voltage is
established with respect to the device GND connection.
Hysteresis
Each comparator has built-in 6.5mV (typical) hysteresis to
simplify designs, ensure stable operation in the presence
of noise at the inputs, and to reject supply rail noise that
might be induced by state change load transients. The
hysteresis is designed such that the falling input threshold
voltage is nominally 393.5mV. External positive feedback
circuitry can be employed with noninverting comparator
inputs to increase effective hysteresis if desired, but such
circuitry will provide an apparent effect on both the rising
and falling input thresholds (the actual internal thresholds
remain unaffected).
Comparator Inputs
A comparator input can swing from ground to 18V (36V
for LT6700HV), regardless of the supply voltage used. The
typical input current for inputs well above threshold (i.e.,
>800mV) is a few pA leaking into an input. With decreasing
input voltage, a small bias current begins to be drawn out
of the input, reaching a few nA when at ground potential.
The input may be forced 100mV below ground without
causing an improper output, though some additional bias
current will begin to flow from the parasitic ESD input pro-
tection diode. Inputs driven further negative than 100mV
below ground will not cause comparator malfunction or
damage (provided the current is limited to 10mA), but
the accuracy of the reference cannot be guaranteed, in
which case the output state of the alternate comparator
may be affected.
Comparator Outputs
The comparator outputs are open collector and capable
of sinking 40mA typical. Load currents are directed out
the GND pin of the part. The output off-state voltage may
range between –0.3V and 18V (36V for LT6700HV) with
respect to ground, regardless of the supply voltage used.
When the output high state bias voltage is above 18V, a
100k minimum pull-up resistor is required and total load
capacitor must be less than 100nF. If the output high state
is above 18V, caution must be taken to prevent a short
from the output directly to the bias voltage, even if the
output is in the off state. As with any open-collector device,
the outputs may be tied together to implement wire-AND
logic functions.
Power Supplies
The comparator family core circuitry operates from a single
1.4V to 18V supply. A minimum 0.1µF bypass capacitor
is required between the V
S
pin and GND. When an output
load is connected to the supply rail near the part and the
output is sinking more than 5mA, a 1µF bypass capaci-
tor is recommended. The voltage reference built into the
LT6700 can be susceptible to high noise on the supply
line, particularly noise that is less than 50kHz and larger
than 20mV
P-P
. In order to reduce the probability of a false
comparator output in the presence of high supply noise,
an RC filter should be used to reduce the noise. This filter
can be created simply by adding a series R between the
system supply and the LT6700 V
S
pin, using the decoupling
capacitor to create a lowpass response. It is recommended
that the filter have a time constant:
t
RC
> V
N
/100
Where V
N
is the peak-peak supply noise in millivolts and
t
RC
is milliseconds.
This filter will also increase the start-up time of the LT6700
by reducing the rate at which the supply can change. When
LT6700/LT6700HV
15
6700123fh
For more information www.linear.com/LT6700
APPLICATIONS INFORMATION
using a supply filter, the start-up time of the LT6700 will
increase to:
t
START
= (0.17ms + 0.25 • t
RC
) • ΔV
S
Where t
START
and t
RC
are in milliseconds and ΔV
S
is the
change in supply in volts. The low supply current of the
LT6700 should not cause significant voltage drop due to
a 2k maximum series R.
Flexible Window Comparator
Using the LT6700-1/LT6700HV-1 as shown in the circuits
of Figure 1, the wire-AND configuration permits high
accuracy window functions to be implemented with a
simple 3-resistor voltage divider network. The section A
comparator provides the V
L
trip-point and the section B
comparator provides the V
H
trip-point, with the built-in
hysteresis providing about 1.7% recovery level at each
trip point to prevent output chatter.
For designs that are to be optimized to detect
departure
from a window limit, the nominal resistor divider values
are selected as follows (refer to the resistor designators
shown on the first circuit of Figure 1):
R1 ≤ 400k (this sets the divider current >> I
B
of inputs)
R2 = R1 • (0.98 • V
H
/V
L
– 1)
R3 = R1 • (2.5 • V
H
– 0.98 • V
H
/V
L
)
To create window functions optimized for detecting
entry
into a window (i.e., where the output is to indicate a “com-
ing into spec” condition, as with the examples in Figure 1),
Figure 1. Simple Window Comparator
the nominal resistor values are selected as follows:
R1 ≤ 400k (this sets the divider current >> I
B
of inputs)
R2 = R1 • (1.02 • V
H
/V
L
– 1)
R3 = R1 • (2.54 • V
H
– 1.02 • V
H
/V
L
)
The worst-case variance of the trip-points is related to
the specified threshold limits of the LT6700/LT6700HV
device and the basic tolerance of divider resistors used.
For resistor tolerance R
TOL
(e.g. 0.01 for 1%), the worst-
case trip-point voltage (either V
H
or V
L
) deviations can be
predicted as follows (italicized values are taken from the
data sheet, expressed in volts):
Max dev V
TRIP
= ±V
TRIPnom
{2 R
TOL
[(V
TRIPnom
– 0.4)
/ V
TRIPnom
] + 1.25 • (
V
TH(R)max
V
TH(R)min
)}
Max dev V
TRIP
= ±V
TRIPnom
{ 2 R
TOL
[(V
TRIPnom
– 0.39)
/ V
TRIPnom
] + 1.27 • (
V
TH(F)max
V
TH(F)min
)}
Generating an External Reference Signal
In some applications, it would be advantageous to have
access to a signal that is directly related to the internal
400mV reference, even though the reference itself is not
available externally. This can be accomplished to a reason-
able degree by using an inverting comparator section as
a “bang-bang” servo, establishing a nominal voltage, on
an integration capacitor, that is scaled to the reference.
This method is used in Figure 2, where the reference level
has been doubled to drive a resistor bridge. The section
B output cycles on and off to swing the section B input
between its hysteresis trip points as the load capacitor
LT6700-1
V
S
GND
R3
301k
R2
6.04k
33k
+INA
–INB OUTB
OUTA
V
OUT
V
S
V
L
V
H
3.3V
3.3V Supply Monitor 5V Supply Monitor
R1
40.2k
V
OUT
HIGH = (3.1V < V
S
< 3.5V)
HYSTERESIS ZONES
APPROXIMATELY
2% OF TRIP VOLTAGE
LT6700-1
V
S
GND
487k
6.04k
33k
+INA
–INB OUTB
OUTA
5V
40.2k
V
OUT
HIGH = (4.7V < V
S
< 5.3V)
6700123 F01
0.1µF 0.1µF

LT6700HDCB-2#TRMPBF

Mfr. #:
Manufacturer:
Analog Devices Inc.
Description:
Analog Comparators uP, L V, 2x Comp w/ 400mV Ref
Lifecycle:
New from this manufacturer.
Delivery:
DHL FedEx Ups TNT EMS
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