AD7869
–9–
Figure 9. ADC FFT Plot
Figure 10 shows a typical plot of effective number of bits versus
frequency for an AD7869AQ with a sampling frequency of
60 kHz. The effective number of bits typically falls between 12.7
and 13.1, corresponding to SNR figures of 79 dB and 80.4 dB.
Figure 10. Effective Number of Bits vs. Frequency for the
ADC
DAC Testing
A simplified diagram of the method used to test the dynamic
performance specifications of the DAC is outlined in Figure 11.
Data is loaded to the DAC under control of the microcontroller
and associated logic. The output of the DAC is applied to a 9th
order low pass filter whose cutoff frequency corresponds to the
Nyquist limit. The output of the filter is, in turn, applied to a
16-bit accurate digitizer. This digitizes the signal and the micro-
controller generates an FFT plot from which the dynamic per-
formance of the DAC can be evaluated.
AD7869
DAC
LOW-PASS
FILTER
16-BIT
DIGITIZER
MICRO-
CONTROLLER
Figure 11. DAC Dynamic Performance Test Circuit
AD7869 DYNAMIC SPECIFICATIONS
The AD7869 is specified and 100% tested for dynamic perfor-
mance specifications as well as traditional dc specifications such
as Integral and Differential Nonlinearity. These ac specifications
are required for signal processing applications such as speech
recognition, spectrum analysis and high speed modems. These
applications require information on the converter’s effect on the
spectral content of the input signal. Hence, the parameters for
which the AD7869 is specified include SNR, harmonic distor-
tion and peak harmonics. These terms are discussed in more de-
tail in the following sections.
Signal-to-Noise Ratio (SNR)
SNR is the measured signal-to-noise ratio at the output of the
ADC or DAC. The signal is the rms magnitude of the funda-
mental. Noise is the rms sum of all the nonfundamental signals
up to half the sampling frequency (f
SAMPLE
/2), excluding dc.
SNR is dependent upon the number of levels used in the quanti-
zation process; the more levels, the smaller the quantization
noise. The theoretical signal-to-noise ratio for a sine wave input
is given by
SNR = (6.02N + 1.76) dB (1)
where N is the number of bits. Thus for an ideal 14-bit con-
verter, SNR = 86 dB.
Effective Number of Bits
The formula given in Equation (1) relates the SNR to the num-
ber of bits. Rewriting the formula, as in Equation (2), it is pos-
sible to obtain a measure of performance expressed in effective
number of bits (N).
N =
SNR –1.76
6.02
(2)
The effective number of bits for a device can be calculated di-
rectly from its measured SNR.
Harmonic Distortion
Harmonic Distortion is the ratio of the rms sum of harmonics to
the fundamental. For the AD7869, total harmonic distortion
(THD) is defined as:
THD =20log
V
2
2
+V
3
2
+V
4
2
+V
5
2
+V
6
2
V
1
where V1 is the rms amplitude of the fundamental and V2, V3,
V4, V5 and V6 are the rms amplitudes of the second through to
the sixth harmonic. The THD is also derived from the FFT plot
of the ADC or DAC output spectrum.
ADC Testing
The output spectrum from the ADC is evaluated by applying a
sine wave signal of very low distortion to the V
IN
input while
reading multiple conversion results. A Fast Fourier Transform
(FFT) plot is generated from which the SNR data can be ob-
tained. Figure 9 shows a typical 2048 point FFT plot of the
AD7869AQ ADC with an input signal of 10 kHz and a sam-
pling frequency of 60 kHz. The SNR obtained from this graph
is 80 dB. It should be noted that the harmonics are taken into
account when calculating the SNR.
REV. B
AD7869
–10–
Performance versus Frequency
The typical performance plots of Figures 14 and 15 show the
AD7869 DAC performance over a wide range of input frequen-
cies at an update rate of 83 kHz. The plot of Figure 14 is with-
out a sample-and-hold on the DAC output while the plot of
Figure 15 is generated with a sample-and-hold on the output.
Figure 14. DAC Performance vs. Frequency (No
Sample-and-Hold)
Figure 15. DAC Performance vs. Frequency (Sample-and-
Hold)
The digitizer sampling is synchronized with the DAC update
rate to ease FFT calculations. The digitizer samples the DAC
output after the output has settled to its new value. Therefore, if
the digitizer were to directly sample the output, it would effec-
tively be sampling a dc value each time. As a result, the dynamic
performance of the DAC would not be measured correctly. Us-
ing the digitizer directly on the DAC output would give better
results than the actual performance of the DAC. Using a filter
between the DAC and the digitizer means that the digitizer
samples a continuously moving signal, and the true dynamic
performance of the AD7869 DAC output is measured.
Figure 12 shows a typical 2048 point Fast Fourier Transform
plot for the AD7869 DAC with an update rate of 83 kHz and an
output frequency of 1 kHz. The SNR obtained from the graph is
82 dBs.
Figure 12. DAC FFT Plot
Some applications will require improved performance versus fre-
quency from the AD7869 DAC. In these applications, a simple
sample-and-hold circuit such as that outlined in Figure 13 will
extend the very good performance of the DAC to 20 kHz. Other
applications will already have an inherent sample-and-hold
function following the AD7869 DAC output. An example of
this type of application is driving a switched capacitor filter
where the updating of the DAC is synchronized with the
switched capacitor filter. This inherent sample-and-hold func-
tion also extends the frequency range performance.
AD7869*
LDAC
LDAC
V
OUT
Q
ADG201HS
S1 D1
IN1
AD711
*ADDITIONAL PINS OMITTED FOR CLARITY
R2
2k2
C9
330pF
1µs
ONE SHOT
DELAY
R1
2k2
Figure 13. DAC Sample-and-Hold Circuit
REV. B
AD7869
–11–
MICROPROCESSOR INTERFACING
Microprocessor interfacing to the AD7869 is via a serial bus that
uses standard protocol compatible with DSP machines. The
communication interface consists of separate transmit (DAC)
and receive (ADC) sections whose operations can be either syn-
chronous or asynchronous with respect to each other. Each sec-
tion has a clock signal, a data signal and a frame or strobe pulse.
Synchronous operation means that data is transmitted from the
ADC and to the DAC at the same time. In this mode, only one
interface clock is needed, and this has to be the ADC clock out;
RCLK must be connected to TCLK. For asynchronous opera-
tion, DAC and ADC data transfers are independent of each
other; the ADC provides the receive clock (RCLK) while the
transmit clock (TCLK) may be provided by the processor or the
ADC or some other external clock source.
Another option to be considered with serial interfacing is the use
of a gated clock. A gated clock means that the device sending
the data switches on the clock when data is ready to be transmit-
ted and three states the clock output when transmission is com-
plete. Only 16 clock pulses are transmitted with the first data bit
being latched into the receiving device on the first falling clock
edge. Ideally, there is no need for frame pulses, however the
AD7869 DAC frame input (
TFS) has to be driven high between
data transmissions. The easiest method is to use RFS to drive
TFS and use only synchronous interfacing. This avoids the use
of interconnects between the processor and AD7869 frame sig-
nals. Not all processors have a gated clock facility; Figure 16
shows an example with the DSP56000.
Table I below shows the number of interconnect lines between
the processor and the AD7869 for the different interfacing
options.
The AD7869 has the ability to use different clocks for transmit-
ting and receiving data. This option, however, exists only on
some processors and normally just one clock (ADC clock) is
used for all communication with the AD7869. For simplicity, all
the interface examples in this data sheet use synchronous inter-
facing and use the ADC clock (RCLK) as an input for the DAC
clock (TCLK). For a better understanding of each of these in-
terfaces, consult the relevant processor data sheet.
AD7869–DSP56000 Interface
Figure 16 shows a typical interface between the AD7869 and
DSP56000. The interface arrangement is synchronous with a
gated clock requiring only three lines of interconnect. The
DSP56000 internal serial control registers have to be configured
for a 16-bit data word with valid data on the first falling clock
edge. Conversion starts and DAC updating are controlled by an
external timer. Data transfers, which occur during ADC conver-
sions, are between the processor receive and transmit shift regis-
ters and the AD7869’s ADC and DAC. At the end of each
16-bit transfer, the DSP56000 receives an internal interrupt in-
dicating the transmit register is empty, and the receive register is
full.
DSP56000
STD
TFS
*ADDITIONAL PINS OMITTED FOR CLARITY
DT
SCK
SRD
RCLK
DR
CONVST
RFS
TIMER
AD7869*
4.7k 2k 4.7k
LDAC
CONTROL
TCLK
5V+
SC0
Figure 16. AD7869–DSP56000 Interface
AD7869–ADSP-2101/2102 Interface
An interface that is suitable for the ADSP-2101 or the ADSP-
2102 is shown in Figure 17. The interface is configured for syn-
chronous, continuous clock operation. The
LDAC is tied low so
the DAC gets updated on the sixteenth falling clock after
TFS
goes low. Alternatively,
LDAC may be driven from a timer as
shown in Figure 16. As with the previous interface, the proces-
sor receives an interrupt after reading or writing to the AD7869
and updates its own internal registers in preparation for the next
data transfer.
ADSP-2101/2
TFS
DT
TCLK
DT
LDAC
TFS
*ADDITIONAL PINS OMITTED FOR CLARITY
RFS
SCLK
DR
RCLK
DR
CONVST
RFS
CONTROL
TIMER
AD7869*
4.7k 2k 4.7k
5V
5V
+
Figure 17. AD7869–ADSP-2101/ADSP-2102 Interface
Table I. Interconnect Lines for Different Interfacing Options
Number of
Configuration Interconnects Signals
Synchronous 4 RCLK, DR, DT and
RFS
(TCLK = RCLK, TFS = RFS)
Asynchronous* 5 or 6 RCLK, DR, RFS, DT, TFS
(TCLK = RCLK or
µP serial CLK)
Synchronous 3 RCLK, DR and DT
Gated Clock (TCLK = RCLK, TFS = RFS)
*5 LINES OF INTERCONNECT WHEN TCLK = RCLK
6 LINES OF INTERCONNECT WHEN TCLK = µP SERIAL CLK
REV. B

AD7869JRZ

Mfr. #:
Manufacturer:
Analog Devices Inc.
Description:
Data Acquisition ADCs/DACs - Specialized 14 BIT ANALOG I/O SYSTEM
Lifecycle:
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