7
LT1317/LT1317B
BLOCK DIAGRAM
W
+
+
+
+
+
+
+
Σ
RAMP
GENERATOR
1.24V
REFERENCE
R
BIAS
V
C
g
m
FB
ENABLE
200mV
A = 2
FF
A1
COMPARATOR
A2
COMPARATOR
ERROR
AMPLIFIER
A4
0.08
DRIVER
SW
GND
1317 BD
Q3
Q
S
600kHz
OSCILLATOR
5
LBO
LBI
SHDN
SHUTDOWN
3
7
1
4
R1
(EXTERNAL)
V
OUT
8
R2
(EXTERNAL)
FB
2
APPLICATIONS INFORMATION
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OPERATION
The LT1317 combines a current mode, fixed frequency
PWM architecture with Burst Mode micropower operation
to maintain high efficiency at light loads. Operation can
best be understood by referring to the Block Diagram.
The error amplifier compares voltage at the FB pin with the
internal 1.24V bandgap reference and generates an error
signal V
C
. When V
C
decreases below the bias voltage on
hysteretic comparator A1, A1’s output goes low, turning
off all circuitry except the 1.24V reference, error amplifier
and low-battery detector. Total current consumption in
this state is 100µA. As output loading causes the FB
voltage to decrease, V
C
increases causing A1’s output to
go high, in turn enabling the rest of the IC. Switch current
is limited to approximately 250mA initially after A1’s
output goes high. If the load is light, the output voltage
(and FB voltage) will increase until A1’s output goes low,
turning off the rest of the LT1317. Low frequency ripple
voltage appears at the output. The ripple frequency is
dependent on load current and output capacitance. This
Burst Mode operation keeps the output regulated and
reduces average current into the IC, resulting in high
efficiency even at load currents of 300µA or less.
If the output load increases sufficiently, A1’s output remains
high, resulting in continuous operation. When the LT1317
is running continuously, peak switch current is controlled
by V
C
to regulate the output voltage. The switch is turned
on at the beginning of each switch cycle. When the sum-
mation of a signal representing switch current and a ramp
generator (introduced to avoid subharmonic oscillations at
duty factors greater than 50%) exceeds the V
C
signal,
comparator A2 changes state, resetting the flip-flop and
turning off the switch. Output voltage increases as switch
current is increased. The output, attenuated by a resistor
divider, appears at the FB pin, closing the overall loop.
Frequency compensation is provided by an external series
RC network and an optional capacitor connected between
the V
C
pin and ground.
Low-battery detector A4’s open collector output (LBO) pulls
low when the LBI pin voltage drops below 200mV. There
is no hysteresis in A4, allowing it to be used as an amplifier
in some applications. The low-battery detector remains
active in shutdown. To enable the converter, SHDN must
be left floating or tied to a voltage between 1.4V and 6V.
8
LT1317/LT1317B
The LT1317B differs from the LT1317 in that the bias point
on A1 is set lower than on the LT1317 so that minimum
switch current can drop below 50mA. Because A1’s bias
point is set lower, there is no Burst Mode operation at light
loads and the device continues switching at constant
frequency. This results in the absence of low frequency
output voltage ripple at the expense of light load efficiency.
The difference between the two devices is clearly illus-
trated in Figure 2. The top two traces in Figure 2 show an
LT1317/LT1317B circuit, using the components indicated
in Figure 1, set to a 3.3V output. Input voltage is 2V. Load
current is stepped from 2mA to 200mA for both circuits.
Low frequency Burst Mode operation voltage ripple is
observed on Trace A, while none is observed on Trace B.
APPLICATIONS INFORMATION
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COMPONENT SELECTION
Inductors
Inductors appropriate for use with the LT1317 must
possess three attributes. First, they must have low core
loss at 600kHz. Most ferrite core units have acceptable
losses at this switching frequency. Inexpensive iron pow-
der cores should be viewed suspiciously, as core losses
can cause significant efficiency penalties at 600kHz. Sec-
ond, the inductor must be able to handle peak switch
current of the LT1317 without saturating. This places a
lower limit on the physical size of the unit. Molded chokes
or chip inductors usually do not have enough core to
support the LT1317 maximum peak switch current and are
unsuitable for the application. Lastly, the inductor should
have low DCR (copper wire resistance) to prevent effi-
ciency-killing I
2
R losses. Linear Technology has identified
several inductors suitable for use with the LT1317. This is
not an exclusive list. There are many magnetics vendors
whose components are suitable for use. A few vendor’s
components are listed in Table 1.
L
C
IN
C
OUT
D
V
OUT
V
IN
GND
MULTIPLE
VIAs
GROUND PLANE
1317 F03
1
2
3
4
8
7
6
5
LT1317
Figure 3. Recommended Component Placement. Traces Carrying
High Current Are Direct. Trace Area at FB Pin and V
C
Pin is Kept
Low. Lead Length to Battery Should be Kept Short.
1ms/DIV 1317 F02
200mA
LT1317
V
OUT
100mV/DIV
AC COUPLED
LT1317B
V
OUT
100mV/DIV
AC COUPLED
2mA
TRACE A
TRACE B
I
LOAD
Figure 2. LT1317 Exhibits Ripple at 2mA Load
During Burst Mode Operation, the LT1317B Does Not
LAYOUT HINTS
The LT1317 switches current at high speed, mandating
careful attention to layout for proper performance.
You
will not get advertised performance with careless layouts.
Figure 3 shows recommended component placement.
Follow this closely in your PC layout. Note the direct path
of the switching loops. Input capacitor C
IN
must
be placed
close (<5mm) to the IC package. As little as 10mm of wire
or PC trace from C
IN
to V
IN
will cause problems such as
inability to regulate or oscillation.
9
LT1317/LT1317B
Table 1. Inductors Suitable for Use with the LT1317
MAX HEIGHT
PART VALUE DCR MFR (mm) COMMENT
LQH3C100 10µH 0.57 Murata-Erie 2.0 Smallest Size,
Limited Current
Handling
DO1608-103 10µH 0.16 Coilcraft 3.0
CD43-100 10µH 0.18 Sumida 3.2
CD54-100 10µH 0.10 Sumida 4.5 Best Efficiency
CTX32CT-100 10µH 0.50 Coiltronics 2.2 1210 Footprint
Capacitor Selection
Low ESR (Equivalent Series Resistance) capacitors should
be used at the output of the LT1317. For most applications
a solid tantalum in a C or D case size works well. Accept-
able capacitance values range from 10µF to 330µF with
ESR falling between 0.1 and 0.5. If component size is
an issue, tantalum capacitors in smaller case sizes can be
used but they have high ESR and output voltage ripple may
reach unacceptable levels.
Ceramic capacitors are an alternative because of their
combination of small size and low ESR. A 10µF ceramic
capacitor will work for some applications but the ex-
tremely low ESR of these capacitors may cause loop
stability problems. Compensation components will need
APPLICATIONS INFORMATION
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to be adjusted to ensure a stable system for the entire input
voltage range. Figure 4 shows a 2V to 3.3V converter with
new values for R
C
and C
C
. Figure 5 details transient
response for this circuit. Also, ceramic caps are prone to
temperature effects and the designer must check loop
stability over the operating temperature range (see section
on Frequency Compensation).
Input bypass capacitor ESR is less critical and smaller
units may be used. If the input voltage source is physically
near the V
IN
pin (<5mm), a 10µF ceramic or a 10µF A case
tantalum is adequate.
Diodes
Most of the application circuits on this data sheet specify
the Motorola MBR0520L surface mount Schottky diode.
In lower current applications, a 1N4148 can be used,
although efficiency will suffer due to the higher forward
drop. This effect is particularly noticeable at low output
voltages. For higher voltage output applications, such as
LCD bias generators, the extra drop is a small percentage
of the output voltage so the efficiency penalty is small. The
low cost of the 1N4148 makes it attractive wherever it can
be used. In through hole applications the 1N5818 is the all
around best choice.
V
IN
SW
FB
LT1317B
L1
10µH
D1
SHDN
R
C
20k
R2
604k
1%
V
OUT
3.3V
R1
1M
1%
C
C
1500pF
1317 F04
C1
10µF
V
IN
2V
C2
10µF
CERAMIC
D1: MBR0520
L1: SUMIDA CD43-100
V
C
GND
Figure 4. 2V to 3.3V Converter with a 10µF Ceramic Output
Capacitor. R
C
and C
C
Have Been Adjusted to Give Optimum
Transient Response.
200µs/DIV 1317 F05
V
OUT
200mV/DIV
AC COUPLED
I
LOAD
5mA TO
200mA
Figure 5. Transient Response for the Circuit of Figure 4.

LT1317CMS8#PBF

Mfr. #:
Manufacturer:
Analog Devices / Linear Technology
Description:
Switching Voltage Regulators Micropower, 600kHz PWM DC/DC Converters
Lifecycle:
New from this manufacturer.
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