PRODUCTION D
A
TA SHEET
Microsemi
Integrated Products Division
11861 Western Avenue, Garden Grove, CA. 92841, 714-898-8121, Fax: 714-893-2570
Page 13
Copyright © 2000
Rev. 1.0, 2005-08-10
WWW.Microsemi .COM
LX1672
Multiple Output LoadSHARE™ PWM
TM
®
THEORY OF OPERATION (CONTINUED)
BI-PHASE, LOADSHARE™ ( PROPORTIONAL METHOD)
The best topology for generating a current ratio at full load and
proportional between full load and no load is shown in figure 9.
The DC voltage difference between LPF1 and VOUT is a voltage
that is proportional to the current flowing in the Phase 1 inductor.
This voltage can be amplified and used to offset the voltage at
LPF2 through a large impedance that will not significantly alter
the characteristics of the low pass filter. At no load there will be
no offset voltage and no offset current between the two phases.
This will give the highest efficiency at no load.
Also a speed up capacitor can be used between the offset
amplifier output and the negative input of the Phase 2 error
amplifier. This will improve the transient response of the Phase 2
output current, so that it will share more equally with phase 1
current during a transient condition.
The use of a MOSFET input amplifier is required for the buffer
to prevent loading the low pass filter. The gain of the offset
amplifier, and the value of Ra and Rb, will determine the ratio of
currents between the phases at full load. Two external amplifiers are
required or this method.
L1,
Switch
Side
L2,
Switch
Side
62k
+
-
PWM
Input
62k
4700pF
62k
Offset
Voltage
Generator
-
+
ESR L1
10mΩ
ESR L2
10mΩ
V
ou
t
1.5V @ 12
A
18
W
Phase 2
Error Amp
Phase 1
Phase 2
V1
V2
1.5V
+73.3mV
1.5V
+46.7mV
7.33A
4.67A
+5V @ 7W
+3.3V @ 11W
LPF2
+
-
+
-
1M
4700pF
LPF1
Offset Amp
Vos
Rf
Rin
Ra
Rb
RF2
FB2
Figure 9 –LoadSHARE™ Using Proportional Control
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PRODUCTION D
A
TA SHEET
Microsemi
Integrated Products Division
11861 Western Avenue, Garden Grove, CA. 92841, 714-898-8121, Fax: 714-893-2570
Page 14
Copyright © 2000
Rev. 1.0, 2005-08-10
WWW.Microsemi .COM
LX1672
Multiple Output LoadSHARE™ PWM
TM
®
THEORY OF OPERATION (CONTINUED)
The circuit in Figure 9 sums a current through a 1MΩ resistor
(Rb) offsetting the phase 2 error amplifier to create an imbalance
in the L1 and L2 currents. Although there are many ways to
calculate component values the approach taken here is to pick Ra,
Rb, R
IN
, V
OUT
, and inductor ESR. A value for the remaining
resistor Rf can then be calculated.
The first decision to be made is the current sharing ratio,
follow the previous examples to understand the basics of
LoadSHARE™. The most common reason to imbalance the
current in the two phases is because of limitations on the
available power from the input rails for each phase. Use the
available input power and total required output power to
determine the inductor currents for each phase.
All references are to Figure 9
1)
Calculate the voltages V1 and V2.
VoutESR1L Current1L1V +×=
VoutESR2L Current2L2V +×=
2)
Select values for Ra and Rb (Ra is typically 62KΩ ; Rb
is typically 1MΩ)
3) Calculate the offset voltage Vos at the output of the offset
amplifier
()
RbRa
Ra
1V2V
2VVos +×
=
4) Calculate the value for Rf
(select a value for R
IN
typically 5KΩ)
=
V1V
VVos
RRf
OUT
OUT
IN
Due to the high impedances in this circuit layout can affect the
actual current ratio by allowing some of the switching waveforms
to couple into the current summing path. It may be necessary to
make some adjustment in Rf after the final layout is evaluated.
Also, the equation for Rf requires very accurate numbers for the
voltages to insure an accurate result.
BI-PHASE, LOADSHARE™ (SERIES RESISTOR METHOD)
A fourth but less desirable way to produce the ratio current
between the two phases is to add a resistor in series with one of the
inductors. This will reduce the current in the inductor that has the
resistor and increase the current in the inductor of the opposite
phase. The example of Figure 7 can be used to determine the
current ratio by adding the value of the series resistor to the ESR
value of the inductor. The added resistance will lower the overall
efficiency
LoadSHARE ERROR SOURCES
With the high DC feedback gain of this second loop, all phase
timing errors, R
DS(On)
mismatch, and voltage differences across the
half bridge drivers are removed from the current sharing accuracy.
The errors in the current sharing accuracy are derived from the
tolerance on the inductor’s ESR and the input offset voltage
specification of the error amplifier. The equivalent circuit is shown
next for an absolute worst case difference of phase currents
between the two inductors.
VOUT
+
-
ESR L2
ESR L1
Phase 2
Phase 1Offset
Error
5mV
V1
V2
Figure 6 – Error Amplitude
Nominal ESR of 6m. ESR ±5%
Max offset Error = 6mV
+5% ESR L1 = 6.3 m
-5% ESR L2 = 5.7 m
1ESRL
V - 1V
A 12 current 1 phase If
OUT
==
mV75.6106.312V1V
3
OUT
=××=
mV.618mV61V2V
=
+
=
A3214.
10x5.7
10x.618
2L ESR
V-2V
current 2 Phase
3
3
OUT
===
Phase 2 current is 2.32A greater than Phase 1.
Input bias current also contributes to imbalance.
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PRODUCTION D
A
TA SHEET
Microsemi
Integrated Products Division
11861 Western Avenue, Garden Grove, CA. 92841, 714-898-8121, Fax: 714-893-2570
Page 15
Copyright © 2000
Rev. 1.0, 2005-08-10
WWW.Microsemi .COM
LX1672
Multiple Output LoadSHARE™ PWM
TM
®
APPLICATION NOTE
O
UTPUT INDUCTOR
The output inductor should be selected to meet the
requirements of the output voltage ripple in steady-state operation
and the inductor current slew-rate during transient. The peak-to-
peak output voltage ripple is:
RIPPLERIPPLE
IESRV ×=
where
s
D
L
VV
ΔI
OUTIN
f
×
=
ΔI is the inductor ripple current, L is the output inductor value
and ESR is the Effective Series Resistance of the output
capacitor.
ΔI should typically be in the range of 20% to 40% of the
maximum output current. Higher inductance results in lower
output voltage ripple, allowing slightly higher ESR to satisfy the
transient specification. Higher inductance also slows the inductor
current slew rate in response to the load-current step change, ΔI,
resulting in more output-capacitor voltage droop. When using
electrolytic capacitors, the capacitor voltage droop is usually
negligible, due to the large capacitance
The inductor-current rise and fall times are:
()
OUTIN
RISE
VV
ΔI
LT
×=
and
OUT
FALL
V
ΔI
LT ×=
The inductance value can be calculated by
s
D
ΔI
VV
L
OUTIN
f
×
=
OUTPUT CAPACITOR
The output capacitor is sized to meet ripple and transient
performance specifications. Effective Series Resistance (ESR) is a
critical parameter. When a step load current occurs, the output
voltage will have a step that equals the product of the ESR and the
current step, ΔI. In an advanced microprocessor power supply, the
output capacitor is usually selected for ESR instead of capacitance
or RMS current capability. A capacitor that satisfies the ESR
requirements usually has a larger capacitance and current capability
than strictly needed. The allowed ESR can be found by:
(
)
EXRIPPLE
VΔIIESR <+×
Where I
RIPPLE
is the inductor ripple current, ΔI is the maximum
load current step change, and V
EX
is the allowed output voltage
excursion in the transient.
Electrolytic capacitors can be used for the output capacitor, but
are less stable with age than tantalum capacitors. As they age, their
ESR degrades, reducing the system performance and increasing the
risk of failure. It is recommended that multiple parallel capacitors
be used, so that, as ESR increase with age, overall performance
will still meet the processor’s requirements.
There is frequently strong pressure to use the least expensive
components possible; however, this could lead to degraded long-
term reliability, especially in the case of filter capacitors.
Microsemi’s demonstration boards use the CDE Polymer AL-EL
(ESRE) filter capacitors, which are aluminum electrolytic, and
have demonstrated reliability. The OS-CON series from Sanyo
generally provides the very best performance in terms of long term
ESR stability and general reliability, but at a substantial cost
penalty. The CDE Polymer AL-EL (ESRE) filter series provides
excellent ESR performance at a reasonable cost. Beware of off-
brand, very low-cost filter capacitors, which have been shown to
degrade in both ESR and general electrolytic characteristics over
time.
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LX1672-05CPW

Mfr. #:
Manufacturer:
Microchip / Microsemi
Description:
Switching Controllers
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