LT6600-10
11
66001fe
APPLICATIONS INFORMATION
currents will be generated through the DC path between
input and output terminals. Minimize these currents to
decrease power dissipation and distortion.
Consider the application in Figure 3. V
MID
sets the output
common mode voltage of the 1st differential amplifi er
inside the LT6600-10 (see the Block Diagram section) at
2.5V. Since the input common mode voltage is near 0V, there
will be approximately a total of 2.5V drop across the series
combination of the internal 402 feedback resistor and the
external 100 input resistor. The resulting 5mA common
mode DC current in each input path, must be absorbed by
the sources V
IN
+
and V
IN
–
. V
OCM
sets the common mode
output voltage of the 2nd differential amplifi er inside the
LT6600-10, and therefore sets the common mode output
voltage of the fi lter. Since in the example, Figure 3, V
OCM
differs from V
MID
by 0.5V, an additional 2.5mA (1.25mA
per side) of DC current will fl ow in the resistors coupling
the 1st differential amplifi er output stage to fi lter output.
Thus, a total of 12.5mA is used to translate the common
mode voltages.
A simple modifi cation to Figure 3 will reduce the DC
common mode currents by 36%. If V
MID
is shorted to
V
OCM
the common mode output voltage of both op amp
stages will be 2V and the resulting DC current will be
8mA. Of course, by AC-coupling the inputs of Figure 3,
the common mode DC current can be reduced to 2.5mA.
Noise
The noise performance of the LT6600-10 can be evaluated
with the circuit of Figure 7.
Given the low noise output of the LT6600-10 and the 6dB
attenuation of the transformer coupling network, it will
be necessary to measure the noise fl oor of the spectrum
analyzer and subtract the instrument noise from the fi lter
noise measurement.
Example: With the IC removed and the 25 resistors
grounded, measure the total integrated noise (e
S
) of the
spectrum analyzer from 10kHz to 10MHz. With the IC
inserted, the signal source (V
IN
) disconnected, and the
input resistors grounded, measure the total integrated
noise out of the fi lter (e
O
). With the signal source
connected, set the frequency to 1MHz and adjust the
amplitude until V
IN
measures 100mV
P-P
. Measure the
output amplitude, V
OUT
, and compute the passband gain
A = V
OUT
/V
IN
. Now compute the input referred integrated
noise (e
IN
) as:
e
IN
=
(e
O
)
2
–(e
S
)
2
A
Table 1 lists the typical input referred integrated noise for
various values of R
IN
.
Figure 8 is plot of the noise spectral density as a function
of frequency for an LT6600-10 with R
IN
= 402 using
the fi xture of Figure 7 (the instrument noise has been
subtracted from the results).
Table 1. Noise Performance
PASSBAND
GAIN (V/V) R
IN
INPUT REFERRED
INTEGRATED NOISE
10kHz TO 10MHz
INPUT REFERRED
NOISE dBm/Hz
4 100 24V
RMS
–149
2 200 34V
RMS
–146
1 402 56V
RMS
–142
The noise at each output is comprised of a differential
component and a common mode component. Using a
transformer or combiner to convert the differential outputs
to single-ended signal rejects the common mode noise and
gives a true measure of the S/N achievable in the system.
Conversely, if each output is measured individually and
the noise power added together, the resulting calculated
noise level will be higher than the true differential noise.
Figure 7. (S8 Pin Numbers)
–
+
0.1µF
0.1µF
2.5V
–2.5V
–
+
LT6600-10
3
4
1
7
2
8
5
6
R
IN
R
IN
25
25
6600 F07
SPECTRUM
ANALYZER
INPUT
50
V
IN
COILCRAFT
TTWB-1010
1:1