TC110
DS21355B-page 4 2002 Microchip Technology Inc.
3.0 DETAILED DESCRIPTION
The TC110 is a PFM/PWM step-up DC/DC controller
for use in systems operating from two or more cells, or
in low voltage, line-powered applications. It uses PWM
as the primary modulation scheme, but automatically
converts to PFM at output duty cycles less than
approximately 25%. The conversion to PFM provides
reduced supply current, and therefore higher operating
efficiency at low loads. The TC110 uses an external
switching transistor, allowing construction of switching
regulators with maximum output currents of 300mA.
The TC110 consumes only 70µA, typical, of supply
current and can be placed in a 0.5µA shutdown mode
by bringing the shutdown input (SHDN
) low. The
regulator remains disabled while in shutdown mode,
and normal operation resumes when SHDN
is brought
high. Other features include start-up at V
IN
= 0.9V and
an externally programmable soft start time.
3.1 Operating Mode
The TC110 is powered by the voltage present on the
V
DD
input. The applications circuits of Figure 3-1 and
Figure 3-2 show operation in the bootstrapped and
non-bootstrapped modes. In bootstrapped mode, the
TC110 is powered from the output (start-up voltage is
supplied by V
IN
through the inductor and Schottky
diode while Q1 is off). In bootstrapped mode, the
switching transistor is turned on harder because its
gate voltage is higher (due to the boost action of the
regulator), resulting in higher output current capacity.
The TC110 is powered from the input supply in the non-
bootstrapped mode. In this mode, the supply current to
the TC110 is minimized. However, the drive applied to
the gate of the switching transistor swings from the
input supply level to ground, so the transistor’s ON
resistance increases at low input voltages. Overall
efficiency is increased since supply current is reduced,
and less energy is consumed charging and discharging
the gate of the MOSFET. While the TC110 is guaran-
teed to start up at 0.9V the device performs to
specifications at 2.0V and higher.
3.2 Low Power Shutdown Mode
The TC110 enters a low power shutdown mode when
SHDN
is brought low. While in shutdown, the oscillator
is disabled and the output switch (internal or external)
is shut off. Normal regulator operation resumes when
SHDN
is brought high. SHDN maybetiedtotheinput
supply if not used.
Note: Because the TC110 uses an external diode,
a leakage path between the input voltage
and the output node (through the inductor
and diode) exists while the regulator is in
shutdown. Care must be taken in system
design to assure the input supply is isolated
from the load during shutdown.
3.3 Soft Start
Soft start allows the output voltage to gradually ramp
from 0V to rated output value during start-up. This
action minimizes (or eliminates) overshoot, and in
general, reduces stress on circuit components.
Figure 3-3 shows the circuit required to implement soft
start (values of 470K and 0.1µFforR
SS
and C
SS
,
respectively, are adequate for most applications).
3.4 Input Bypass Capacitors
Using an input bypass capacitor reduces peak current
transients drawn from the input supply and reduces the
switching noise generated by the regulator. The source
impedance of the input supply determines the size of
the capacitor that should be used.
2002 Microchip Technology Inc. DS21355B-page 5
TC110
FIGURE 3-1: BOOTSTRAPPED OPERATION
FIGURE 3-2: NON-BOOTSTRAPPED OPERATION
FIGURE 3-3: SOFT START/SHUTDOWN CIRCUIT
5
4
TC110XX
1
3
2
V
OUT
EXT
GND
D1
IN5817
C2
47µF
L1
100µH
V
OUT
OFF
ON
n
MTP3055EL
C1
33µF
V
IN
SHDN
V
DD
+
5
4
TC110XX
1
3
2
V
OUT
EXT
GND
D1
IN5817
C2
47µF
L1
100µH
V
OUT
OFF
ON
n
MTP3055EL
C1
33µF
V
IN
SHDN
V
DD
+
TC110XX
3
SHDN/SS
C
SS
0.1µF
SHDN
R
SS
470K
V
IN
TC110XX
3
SHDN/SS
C
SS
0.1µF
R
SS
470K
Shutdown Used
Shutdown Not Used
TC110
DS21355B-page 6 2002 Microchip Technology Inc.
3.5 Output Capacitor
The effective series resistance of the output capacitor
directly affects the amplitude of the output voltage
ripple. (The product of the peak inductor current and
the ESR determines output ripple amplitude.) There-
fore, a capacitor with the lowest possible ESR should
be selected. Smaller capacitors are acceptable for light
loads or in applications where ripple is not a concern.
The Sprague 595D series of tantalum capacitors are
among the smallest of all low ESR surface mount
capacitors available. Table 4-1 lists suggested
components and suppliers.
3.6 Inductor Selection
Selecting the proper inductor value is a trade-off
between physical size and power conversion require-
ments. Lower value inductors cost less, but result in
higher ripple current and core losses. They are also
more prone to saturate since the coil current ramps
faster and could overshoot the desired peak value. This
not only reduces efficiency, but could also cause the
current rating of the external components to be
exceeded. Larger inductor values reduce both ripple
current and core losses, but are larger in physical size
and tend to increase the start-up time slightly.
A22µH inductor is recommended for the 300kHz
versions and a 47µH inductor is recommended for the
100kHz versions. Inductors with a ferrite core (or
equivalent) are also recommended. For highest
efficiency, use inductors with a low DC resistance (less
than 20 m).
The inductor value directly affects the output ripple
voltage. Equation 3-3 is derived as shown below, and
can be used to calculate an inductor value, given the
required output ripple voltage and output capacitor
series resistance:
EQUATION 3-1:
where ESR is the equivalent series resistance of the
output filter capacitor, and V
RIPPLE
is in volts.
Expressing di in terms of switch ON resistance and
time:
EQUATION 3-2:
Solving for L:
EQUATION 3-3:
Care must be taken to ensure the inductor can handle
peak switching currents, which can be several times
load currents. Exceeding rated peak current will result
in core saturation and loss of inductance. The inductor
should be selected to withstand currents greater than
I
PK
(Equation 3-10) without saturating.
Calculating the peak inductorcurrent is straightforward.
Inductor current consists of an AC (sawtooth) current
centered on an average DC current (i.e., input current).
Equation 3-6 calculates the average DC current. Note
that minimum input voltage and maximum load current
values should be used:
EQUATION 3-4:
Re-writing in terms of input and output currents and
voltages:
EQUATION 3-5:
Solving for input curent:
EQUATION 3-6:
The sawtooth current is centered on the DC current
level; swinging equally above and below the DC current
calculated in Equation 3-6. The peak inductor current is
the sum of the DC current plus half the AC current.
Note that minimum input voltage should be used when
calculating the AC inductor current (Equation 3-9).
EQUATION 3-7:
EQUATION 3-8:
EQUATION 3-9:
where: V
SW
=V
CESAT
oftheswitch(noteifaCMOS
switch is used substitute V
CESAT
for r
DSON
xI
IN
)
Combining the DC current calculated in Equation 3-6,
with half the peak AC current calculated in Equation 3-
9, the peak inductor current is given by:
EQUATION 3-10:
V
RIPPLE
ESR(di)
V
RIPPLE
ESR [(V
IN
–V
SW
)t
ON
]
L
ESR [(V
IN
–V
SW
)t
ON
]
V
RIPPLE
L
=
Output Power
Efficiency
Input Power
(V
OUTMAX
)(I
OUTMAX
)
Efficiency
(V
INMIN
)(I
INMAX
)=
(V
OUTMAX
)(I
OUTMAX
)
(Efficiency)(V
INMAX
)
I
INMAX
=
=
L(di)
dt
V
=
V(dt)
dt
di
[(V
INMIN
–V
SW
)t
ON
]
L
di =
I
PK
=I
IN
MAX
+0.5(di)

TC110331ECTTR

Mfr. #:
Manufacturer:
Microchip Technology
Description:
Switching Controllers PFM/PWM Step-Up
Lifecycle:
New from this manufacturer.
Delivery:
DHL FedEx Ups TNT EMS
Payment:
T/T Paypal Visa MoneyGram Western Union