IR3529
Page 7 of 22 February 12, 2010
PIN DESCRIPTION
PIN# PIN SYMBOL PIN DESCRIPTION
1 ILL Output of the Current Sense Amplifier is connected to this pin through a 3k
resistor. Voltage on this pin is equal to V(DACIN) + 33 [V(CSIN+) – V(CSIN-)].
Connecting all ILL pins together creates a bus which provides an indication of the
average current being supplied by the power supply. The signal is used by the
Control IC for voltage positioning and over-current protection. OVP mode is initiated
if the voltage on this pin rises above V(VCCL)- 0.8V.
2 PSI# Digital Power State Indicator input, active low.
3 DACIN Reference voltage input from the Control IC. The Current Sense signal and PWM
ramp is referenced to the voltage on this pin.
4 LGND Ground for internal IC circuits. IC substrate is connected to this pin.
5 PHSIN Phase clock input at switching frequency.
6 SHIFT Communication input from phase IC(s) statically floats at VCCL/2. Momentarily
pulling pin up to VCCL indicates a phase has entered the daisy chain loop resulting
in an up-shift in the CLKOUT frequency. Momentarily pulling down to ground
indicates a loss of a phase and down-shifts the CLKOUT frequency.
7 PHSOUT Phase clock output at switching frequency.
8 CLKIN Clock input.
9 PGND Return for low side driver and reference for GATEH non-overlap comparator.
10 GATEL Low-side driver output and input to GATEH non-overlap comparator.
11 OCSET Programs cycle by cycle Over Current threshold voltage. V(OCSET) gets compared
against the V(SW) node when the high side MOSFET is on. If V(SW) gets below
V(OCSET), the next switch pulse gets skipped to allow inductor relaxation. The
V(OCSET) threshold is programmed by forcing a 200uA current sink through an
external resistor kelvined to the drain of the high side FET.
12 VCCL Supply for low-side driver. Internal bootstrap synchronous PFET is connected from
this pin to the BOOST pin.
13 BOOST Supply for high-side driver. Internal bootstrap synchronous PFET is connected
between this pin and the VCCL pin.
14 GATEH High-side driver output and input to GATEL non-overlap comparator.
15 SW Return for high-side driver and reference for GATEL non-overlap comparator.
16 VCC Supply for internal IC circuits.
17 CSIN+ Non-Inverting input to the current sense amplifier, and input to debug comparator.
18 CSIN- Inverting input to the current sense amplifier, and input to synchronous rectification
disable comparator.
19 EAIN PWM comparator input from the error amplifier output of Control IC. Body Braking
mode is initiated if the voltage on this pin is less than V(DACIN).
20 ISHARE Output of the Current Sense Amplifier is connected to this pin through a 3k
resistor. Voltage on this pin is equal to V(DACIN) + 33 [V(CSIN+) – V(CSIN-)].
Connecting all ISHARE pins together creates a share bus which provides an
indication of the average current being supplied by active phases only. The pin
becomes high impedance during PSI# activation.
IR3529
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SYSTEM THEORY OF OPERATION
System Description
The system consists of one control IC and a scalable array of phase converters, each requiring one phase IC. The
control IC communicates with the phase ICs using three digital buses, i.e., CLOCK, PHSIN, PHSOUT and three analog
buses, i.e., DAC, EA, and IOUT. The digital buses are responsible for switching frequency determination and accurate
phase timing control without any external components. The analog buses are used for PWM control and current
sharing between interleaved phases. The control IC incorporates all the system functions, i.e., VID, CLOCK signals,
error amplifier, fault protections, current monitor, etc. The Phase IC implements the functions required by the converter
of each phase, i.e., the gate drivers, PWM comparator and latch, over-voltage protection, phase disable circuit, current
sensing and sharing, etc.
PWM Control Method
The PWM block diagram of the XPhase3
TM
architecture is shown in Figure 1. Feed-forward voltage mode control with
trailing edge modulation is used. A high-gain and wide-bandwidth voltage type error amplifier is implemented in the
controller’s design to achieve a fast voltage control loop. Input voltage is sensed by the phase ICs to provide feed-
forward control. The feed-forward control compensates the ramp slope based on the change in input voltage. The input
voltage can change due to variations in the silver box output voltage or due to the wire and PCB-trace voltage drop
related to changes in load current.
VID6
VID6
VID6
VID6
VID6
VID6
VID6
VID6
PSI# C OMPARATOR
&
8 COU NT DELAY
PWM C OMPARATOR
&
LATCH
VID6
VID6
VID6
VID6
VID6
VID6
VID6
VID6
VID6
VID6
PWM C OMPARATOR
&
LATCH
PSI# COMPARATOR
&
8 CO UN T DELAY
VID6
VID6
VID6
SHIF T
PULSE
GENERATION
VID6
VID6
VID6
VID6
VID6
OFF
CLK
D
Q
OFF
VID6
VID6
VID6
VID6
+
+
CURRENT
SENSE
AMPLIFIER
BODY
BRAKING
SHARE ADJUST
AMPLIFIER
1 2
PHASE IC
VID6
VID6
VID6
SHIF T
PULSE
GENERATION
VID6
VID6
VID6
VID6
SHIFT
VID6
PSI
ILL
NO. OF ACTIVE PHASES MONITOR
SHIFT
RDR P1
CLKIN
VSETPT
RCS
ISHARE
PHSIN
DACIN
VCC
EAIN
GATEH
CCS
VCCH
CSIN-
CSIN+
GATEL
PGND
VCCL
CBST
SW
RTHRM
PHSOUT
VID6
VID6
OFF
RCOMP
PHSIN
CLK
D
Q
OFF
PSI
CCOMP
RFB
+
-
CLKIN
CDR P
RCS
+
-
+
-
CCS
VOUT
GND
RDR P
VDAC
VO
VOSNS+
DACIN
VCC
ISHARE
PHSIN
VOSNS-
GATEL
EAIN
GATEH
IIN
VDRP
LGND
FB
EAOUT
CLKOUT
CSIN-
CSIN+
VIN
IROSC
VDAC
REMOTE SENSE
AMPLIFIER
VID6
VCCH
CBST
VCCL
GATE DRIVE
VOLTAGE
PHSOUT
VID6
PSI
RVSETPT
PGND
VID6
SW
VID6
+
+
-
+
Thermal
Compensation
VN
VDAC
BODY
BRAKING
VDRP
AMP
IVSETPT
CURRENT
SENSE
AMPLIFIER
CLOCK GENERATOR
IMON
ERROR
AMPLIFIER
SHARE ADJUST
AMPLIFIER
RFB1
CONTROL IC
COU T
PSI#
CFB1
1 2
PHASE IC
PHSOUT
VID6
SHIFT
SHIFT
ILL
Figure 1: PWM Block Diagram
IR3529
Page 9 of 22 February 12, 2010
Frequency and Phase Timing Control
The oscillator is located in the Control IC and the system clock frequency is programmable from 250 kHz to 9 MHz by
an external resistor. The control IC system clock signal (CLKOUT) is connected to CLKIN of all the phase ICs. The
phase timing of the phase ICs is controlled by the daisy chain loop, where the control IC phase clock output (PHSOUT)
is connected to the phase clock input (PHSIN) of the first phase IC, and PHSOUT of the first phase IC is connected to
PHSIN of the second phase IC, etc. The last phase IC is connected back to PHSIN of the control IC to complete the
daisy chain loop. During power up, the control IC sends out clock signals from both CLKOUT and PHSOUT pins and
detects the feedback at PHSIN pin to determine the phase number and monitor any fault in the daisy chain loop. When
the PSI is asserted (active low), the phases are effectively removed from the daisy chain loop. Figure 2 shows the
phase timing for a four phase converter. The switching frequency is set by the resistor ROSC. The clock frequency
equals the number of phase times the switching frequency.
Phase IC1
PWM Latch SET
Control IC CLKOUT
(Phase IC CLKIN)
Control IC PHSOUT
(Phase IC1 PHSIN)
Phase IC 1 PHSOUT
(Phase IC2 PHSIN)
Phase IC 2 PHSOUT
(Phase IC3 PHSIN)
Phase IC 3 PHSOUT
(Phase IC4 PHSIN)
Phase IC4 PHSOUT
(Control IC PHSIN)
Figure 2: Four Phase Oscillator Waveforms
PWM Operation
The PWM comparator is located in the phase IC. Upon receiving the falling edge of a clock pulse, the PWM latch is set
and the PWM ramp voltage begins to increase. In addition, the low side driver is turned off and the high side driver is
turned on after the non-overlap time expires (GATEL < 1V). When the PWM ramp voltage exceeds the error amplifier’s
output voltage, the PWM latch is reset and the internal ramp capacitor is quickly discharged to the output of the share
adjust amplifier and remains discharged until the next clock pulse. This reset latch additionally turns off the high side
driver and enables the low side driver after the non-overlap time concludes (Switch Node < 1V).
The PWM latch is reset dominant allowing all phases to go to zero duty cycle within a few tens of nanoseconds in
response to a load step decrease. Phases can overlap and go up to 100% duty cycle in response to a load step
increase with turn-on gated by the clock pulses. An error amplifier output voltage greater than the common mode input
range of the PWM comparator, results in 100% duty cycle regardless of the voltage of the PWM ramp. This
arrangement guarantees that the error amplifier is always in control and can demand 0 to 100% duty cycle as required.
It also favors response to a load step decrease, which is appropriate, given that the low output to input voltage ratio of
most systems. The inductor current will increase much more rapidly than decrease in response to load transients.
This control method is designed to provide “single cycle transient response.” The inductor current will change in
response to load transients within a single switching cycle maximizing the effectiveness of the power train and
minimizing the output capacitor requirements. An additional advantage of the architecture is that differences in ground
or input voltage, at the phases, have no effect on operation since the PWM ramps are referenced to VDAC. Figure 3
depicts PWM operating waveforms under various conditions.

IR3529MTRPBF

Mfr. #:
Manufacturer:
Infineon Technologies
Description:
Power Management Specialized - PMIC 2 CH OR 2 PHASE SYNC PWM CNTRLR
Lifecycle:
New from this manufacturer.
Delivery:
DHL FedEx Ups TNT EMS
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