MAX1630A–MAX1635A
Multi-Output, Low-Noise Power-Supply
Controllers for Notebook Computers
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Current-Sense Resistor Value
The current-sense resistor value is calculated according
to the worst-case-low current-limit threshold voltage
(from the Electrical Characteristics table) and the peak
inductor current:
Use I
PEAK
from the second equation in the Inductor
Value section
Use the calculated value of R
SENSE
to size the MOSFET
switches and specify inductor saturation-current ratings
according to the worst-case high-current-limit threshold
voltage:
Low-inductance resistors, such as surface-mount
metal-film, are recommended.
Input Capacitor Value
Connect low-ESR bulk capacitors and small ceramic
capacitors (0.1µF) directly to the drains on the high-side
MOSFETs. The bulk input filter capacitor is usually
selected according to input ripple current requirements
and voltage rating, rather than capacitor value.
Electrolytic capacitors with low enough effective series
resistance (ESR) to meet the ripple current requirement
invariably have sufficient capacitance values. Aluminum
electrolytic capacitors, such as Sanyo
OS-CON or Nichicon PL, are superior to tantalum types,
which carry the risk of power-up surge-current failure,
especially when connecting to robust AC adapters or
low-impedance batteries. RMS input ripple current
(I
RMS
) is determined by the input voltage and load cur-
rent, with the worst case occurring at V
IN
= 2 x V
OUT
:
Bypassing V+
Bypass the V+ input with a 4.7µF tantalum capacitor
paralleled with a 0.1µF ceramic capacitor, close to the
IC. A 10Ω series resistor to V
IN
is also recommended.
Bypassing VL
Bypass the VL output with a 4.7µF tantalum capacitor
paralleled with a 0.1µF ceramic capacitor, close to the
device.
Output Filter Capacitor Value
The output filter capacitor values are generally deter-
mined by the ESR and voltage rating requirements, rather
than actual capacitance requirements for loop stability. In
other words, the low-ESR electrolytic capacitor that meets
the ESR requirement usually has more output capaci-
tance than is required for AC stability. Use only special-
ized low-ESR capacitors intended for switching-regulator
applications, such as AVX TPS, Sprague 595D, Sanyo
OS-CON, or Nichicon PL series. To ensure stability, the
capacitor must meet both minimum capacitance and
maximum ESR values as given in the following equations:
(can be multiplied by 1.5; see text below)
These equations are worst case, with 45 degrees of
phase margin to ensure jitter-free, fixed-frequency
operation and provide a nicely damped output
response for zero to full-load step changes. Some cost-
conscious designers may wish to bend these rules with
less-expensive capacitors, particularly if the load lacks
large step changes. This practice is tolerable if some
bench testing over temperature is done to verify
acceptable noise and transient response.
No well-defined boundary exists between stable and
unstable operation. As phase margin is reduced, the
first symptom is a bit of timing jitter, which shows up as
blurred edges in the switching waveforms where the
scope does not quite sync up. Technically speaking,
this jitter (usually harmless) is unstable operation, since
the duty factor varies slightly. As capacitors with higher
ESRs are used, the jitter becomes more pronounced,
and the load-transient output voltage waveform starts
looking ragged at the edges. Eventually, the load-tran-
sient waveform has enough ringing on it that the peak
noise levels exceed the allowable output voltage toler-
ance. Note that even with zero phase margin and gross
instability present, the output voltage noise never gets
much worse than I
PEAK
x R
ESR
(under constant loads).
Designers of RF communicators or other noise-sensi-
tive analog equipment should be conservative and stay
within the guidelines. Designers of notebook computers
and similar commercial-temperature-range digital
systems can multiply the R
ESR
value by a factor of 1.5
without hurting stability or transient response.
The output voltage ripple is usually dominated by the
filter capacitor’s ESR, and can be approximated as
I
RIPPLE
x R
ESR
. There is also a capacitive term, so the
