CS51411, CS51412, CS51413, CS51414
http://onsemi.com
13
turns P1 on and current is routed to the internal bias circuitry
from the BIAS pin.
Here is an example of the power savings:
The input voltage range for V
in
is 4.5 V to 40 V. The input
voltage range for BIAS is 3.3 V to 6 V. The quiescent current
specification is 3 mA (min), 4 mA (typ), and 6.25 mA (max).
Using a typical battery voltage of 14 V and the typical
quiescent current number of 4 mA, the power would be:
P + V I + 14 4e3 + 56 mW
We’ll assume the BIAS pin is connected to an external
regulator at 5 V instead of the output voltage. The BIAS pin
would normally be connected to the output voltage, but
adding an added switching regulator efficiency number here
would cloud this example. Now the internal BIAS circuitry
is being powered via 5 V. The resulting on chip power being
dissipated is:
P + V I + 5 4e3 + 21 mW
The power savings is 35 mW.
Now, to demonstrate more notable savings using the
maximum battery input voltage of 40 V, the maximum
quiescent current of 6.25 mA, and the lowest allowed BIAS
voltage for proper operation of 3.3 V;
Powered from V
in
:
P + 40 6.25e3 + 250 mW
Powered from the BIAS pin:
P + 3.3 6.25e3 + 21 mW
The power savings is 229 mW.
Minimum Load Requirement
As pointed out in the previous section, a minimum load is
required for this regulator due to the predriver current
feeding the output. Placing a resistor equal to V
O
divided by
12 mA should prevent any voltage overshoot at light load
conditions. Alternatively, the feedback resistors can be
valued properly to consume 12 mA current.
COMPONENT SELECTION
Input Capacitor
In a buck converter, the input capacitor witnesses pulsed
current with an amplitude equal to the load current. This
pulsed current and the ESR of the input capacitors determine
the V
IN
ripple voltage, which is shown in Figure 19. For V
IN
ripple, low ESR is a critical requirement for the input
capacitor selection. The pulsed input current possesses a
significant AC component, which is absorbed by the input
capacitors.
The RMS current of the input capacitor can be calculated
using:
I
RMS
+ I
O
D(1 * D)
Ǹ
where:
D = switching duty cycle which is equal to V
O
/V
IN
.
I
O
= load current.
Figure 19. Input Voltage Ripple in a Buck Converter
To calculate the RMS current, multiply the load current
with the constant given by Figure 20 at each duty cycle. It is
a common practice to select the input capacitor with an RMS
current rating more than half the maximum load current. If
multiple capacitors are paralleled, the RMS current for each
capacitor should be the total current divided by the number
of capacitors.
Figure 20. Input Capacitor RMS Current can be
Calculated by Multiplying Y Value with Maximum Load
Current at any Duty Cycle
0 0.2 0.4 1.0
DUTY CYCLE
0
0.1
0.3
0.4
0.5
0.6
0.2
0.6 0.8
I
RMS
(XI
O
)
Selecting the capacitor type is determined by each
design’s constraint and emphasis. The aluminum
electrolytic capacitors are widely available at lowest cost.
Their ESR and Equivalent Series Inductor (ESL) are
relatively high. Multiple capacitors are usually paralleled to
achieve lower ESR. In addition, electrolytic capacitors
usually need to be paralleled with a ceramic capacitor for
filtering high frequency noises. The OSCON are solid
aluminum electrolytic capacitors, and therefore has a much
lower ESR. Recently, the price of the OSCON capacitors
has dropped significantly so that it is now feasible to use
them for some low cost designs. Electrolytic capacitors are
CS51411, CS51412, CS51413, CS51414
http://onsemi.com
14
physically large, and not used in applications where the size,
and especially height is the major concern.
Ceramic capacitors are now available in values over 10 mF.
Since the ceramic capacitor has low ESR and ESL, a single
ceramic capacitor can be adequate for both low frequency
and high frequency noises. The disadvantage of ceramic
capacitors are their high cost. Solid tantalum capacitors can
have low ESR and small size. However, the reliability of the
tantalum capacitor is always a concern in the application
where the capacitor may experience surge current.
Output Capacitor
In a buck converter, the requirements on the output
capacitor are not as critical as those on the input capacitor.
The current to the output capacitor comes from the inductor
and thus is triangular. In most applications, this makes the
RMS ripple current not an issue in selecting output
capacitors.
The output ripple voltage is the sum of a triangular wave
caused by ripple current flowing through ESR, and a square
wave due to ESL. Capacitive reactance is assumed to be
small compared to ESR and ESL. The peaktopeak ripple
current of the inductor is:
I
P * P
+
V
O
(V
IN
* V
O
)
(V
IN
)(L)(f
S
)
V
RIPPLE(ESR)
, the output ripple due to the ESR, is equal
to the product of I
PP
and ESR. The voltage developed
across the ESL is proportional to the di/dt of the output
capacitor. It is realized that the di/dt of the output capacitor
is the same as the di/dt of the inductor current. Therefore,
when the switch turns on, the di/dt is equal to (V
IN
V
O
)/L,
and it becomes V
O
/L when the switch turns off. The total
ripple voltage induced by ESL can then be derived from
V
RIPPLE(ESL)
+ ESL(
V
IN
L
) ) ESL(
V
IN
* V
O
L
) + ESL(
V
IN
L
)
The total output ripple is the sum of the V
RIPPLE(ESR)
and
V
RIPPLE(ESR)
.
Figure 21. The Output Voltage Ripple Using Two 10 mF
Ceramic Capacitors in Parallel
Figure 22. The Output Voltage Ripple Using One 100 mF
POSCAP Capacitor
Figure 23. The Output Voltage Ripple Using
One 100 mF OSCON
Figure 24. The Output Voltage Ripple Using
One 100 mF Tantalum Capacitor
CS51411, CS51412, CS51413, CS51414
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15
Figure 21 to Figure 24 show the output ripple of a 5.0 V
to 3.3 V/500 mA regulator using 22 mH inductor and various
capacitor types. At the switching frequency, the low ESR
and ESL make the ceramic capacitors behave capacitively
as shown in Figure 21. Additional paralleled ceramic
capacitors will further reduce the ripple voltage, but
inevitably increase the cost. “POSCAP”, manufactured by
SANYO, is a solid electrolytic capacitor. The anode is
sintered tantalum and the cathode is a highly conductive
polymerized organic semiconductor. TPC series, featuring
low ESR and low profile, is used in the measurement of
Figure 22. It is shown that POSCAP presents a good balance
of capacitance and ESR, compared with a ceramic capacitor.
In this application, the low ESR generates less than 5.0 mV
of ripple and the ESL is almost unnoticeable. The ESL of the
throughhole OSCON capacitor give rise to the inductive
impedance. It is evident from Figure 23 which shows the
step rise of the output ripple on the switch turnon and large
spike on the switch turnoff. The ESL prevents the output
capacitor from quickly charging up the parasitic capacitor of
the inductor when the switch node is pulled below ground
through the catch diode conduction. This results in the spike
associated with the falling edge of the switch node. The D
package tantalum capacitor used in Figure 24 has the same
footprint as the POSCAP, but doubles the height. The ESR
of the tantalum capacitor is apparently higher than the
POSCAP. The electrolytic and tantalum capacitors provide
a lowcost solution with compromised performance. The
reliability of the tantalum capacitor is not a serious concern
for output filtering because the output capacitor is usually
free of surge current and voltage.
Diode Selection
The diode in the buck converter provides the inductor
current path when the power switch turns off. The peak
reverse voltage is equal to the maximum input voltage. The
peak conducting current is clamped by the current limit of
the IC. The average current can be calculated from:
I
D(AVG)
+
I
O
(V
IN
* V
O
)
V
IN
The worse case of the diode average current occurs during
maximum load current and maximum input voltage. For the
diode to survive the short circuit condition, the current rating
of the diode should be equal to the Foldback Current Limit.
See Table 1 for Schottky diodes from ON Semiconductor
which are suggested for CS5141X regulator.
Inductor Selection
When choosing inductors, one might have to consider
maximum load current, core and copper losses, component
height, output ripple, EMI, saturation and cost. Lower
inductor values are chosen to reduce the physical size of the
inductor. Higher value cuts down the ripple current, core
losses and allows more output current. For most
applications, the inductor value falls in the range between
2.2 mH and 22 mH. The saturation current ratings of the
inductor shall not exceed the I
L(PK)
, calculated according to
I
L(PK)
+ I
O
)
V
O
(V
IN
* V
O
)
2(f
S
)(L)(V
IN
)
The DC current through the inductor is equal to the load
current. The worse case occurs during maximum load
current. Check the vendor’s spec to adjust the inductor value
undercurrent loading. Inductors can lose over 50% of
inductance when it nears saturation.
The core materials have a significant effect on inductor
performance. The ferrite core has benefits of small physical
size, and very low power dissipation. But be careful not to
operate these inductors too far beyond their maximum
ratings for peak current, as this will saturate the core.
Powered Iron cores are low cost and have a more gradual
saturation curve. The cores with an open magnetic path, such
as rod or barrel, tend to generate high magnetic field
radiation. However, they are usually cheap and small. The
cores providing a close magnetic loop, such as potcore and
toroid, generate low electromagnetic interference (EMI).
There are many magnetic component vendors providing
standard product lines suitable for CS5141X. Table 2 lists
three vendors, their products and contact information.

CS51414EMNR2G

Mfr. #:
Manufacturer:
ON Semiconductor
Description:
Switching Voltage Regulators 1.5A 520kHz BUCK REG LOW VOLTAGE
Lifecycle:
New from this manufacturer.
Delivery:
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