LTC3835
22
3835fe
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APPLICATIONS INFORMATION
most critical frequency range of the feedback loop. The
output voltage settling behavior is related to the stability
of the closed-loop system and will demonstrate the actual
overall supply performance.
A second, more severe transient is caused by switching
in loads with large (>1µF) supply bypass capacitors. The
discharged bypass capacitors are effectively put in parallel
with C
OUT
, causing a rapid drop in V
OUT
. No regulator can
alter its delivery of current quickly enough to prevent this
sudden step change in output voltage if the load switch
resistance is low and it is driven quickly. If the ratio of
C
LOAD
to C
OUT
is greater than 1:50, the switch rise time
should be controlled so that the load rise time is limited
to approximately 25 • C
LOAD
. Thus a 10µF capacitor would
require a 250µs rise time, limiting the charging current
to about 200mA.
Design Example
As a design example, assume V
IN
= 12V(nominal), V
IN
=
22V(max), V
OUT
= 1.8V, I
MAX
= 5A, and f = 250kHz.
The inductance value is chosen first based on a 30% ripple
current assumption. The highest value of ripple current
occurs at the maximum input voltage. Tie the PLLLPF
pin to GND, generating 250kHz operation.
The minimum
inductance for 30% ripple current is:
I
L
=
V
OUT
(f)(L)
1
V
OUT
V
IN
A 4.7µH inductor will produce 23% ripple current and a
3.3µH will result in 33%. The peak inductor current will be
the maximum DC value plus one half the ripple current, or
5.84A, for the 3.3µH value. Increasing the ripple current will
also help ensure that the minimum on-time of 180ns is not
violated. The minimum on-time occurs at maxi-mum V
IN
:
t
ON(MIN )
=
V
OUT
V
IN(MAX )
f
=
1.8V
22V(250kHz)
= 327ns
The R
SENSE
resistor value can be calculated by using the
maximum current sense voltage specification with some
accommodation for tolerances:
R
SENSE
80mV
5.84A
0.012
Choosing 1% resistors: R1 = 25.5k and R2 = 32.4k yields
an output voltage of 1.816V.
The power dissipation on the top side MOSFET can be easily
estimated. Choosing a Fairchild FDS6982S dual MOSFET
results in: R
DS(ON)
= 0.035Ω/0.022Ω, C
MILLER
= 215pF.
At maximum input voltage with T(estimated) = 50°C:
P
MAIN
=
1.8V
22V
5
( )
2
1+(0.005)(50°C 25°C)
[ ]
0.035
( )
+ 22V
( )
2
5A
2
4
( )
215pF
( )
1
5 2.3
+
1
2.3
300kHz
( )
= 332mW
A short-circuit to ground will result in a folded back
current of:
I
SC
=
25mV
0.01
1
2
120ns(22V)
3.3µH
= 2.1A
with a typical value of R
DS(ON)
and d = (0.005/°C)(20) = 0.1.
The resulting power dissipated in the bottom MOSFET is:
P
SYNC
=
22V 1.8V
22V
2.1A
( )
2
1.125
( )
0.022
( )
= 100mW
which is less than under full-load conditions.
C
IN
is chosen for an RMS current rating of at least 3A at
temperature assuming only this channel is on. COUT is
chosen with an ESR of 0.02Ω for low output ripple. The
output ripple in continuous mode will be highest at the
maximum input voltage. The output voltage ripple due to
ESR is approximately:
V
ORIPPLE
= R
ESR
(∆I
L
) = 0.02Ω(1.67A) = 33mV
P–P
LTC3835
23
3835fe
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APPLICATIONS INFORMATION
PC Board Layout Checklist
When laying out the printed circuit board, the following
checklist should be used to ensure proper operation of
the IC. These items are also illustrated graphically in the
layout diagram of Figure 9. The Figure 10 illustrates the
current waveforms present in the various branches of the
synchronous regulator operating in the continuous mode.
Check the following in your layout:
1. Is the top N-channel MOSFET M1 located within 1cm
of C
IN
?
2. Are the signal and power grounds kept separate? The
combined IC signal ground pin and the ground return
of C
INTVCC
must return to the combined C
OUT
(–) termi-
nals. The path formed by the top N-channel MOSFET,
Schottky diode and the C
IN
capacitor should have short
leads and PC trace lengths. The output capacitor (–)
terminals should be connected as close as possible
to the (–) terminals of
the input capacitor by placing
the capacitors next to each other and away from the
Schottky loop described above.
3. Does the LTC3835 V
FB
pin resistive divider connect to the
(+) terminals of C
OUT
? The resistive divider must be con-
nected between the (+) terminal of C
OUT
and signal ground.
The feedback resistor connections should not be along the
high current input feeds from the input capacitor(s).
4. Are the SENSE
and SENSE
+
leads routed together with
minimum PC trace spacing? The filter capacitor between
SENSE
+
and SENSE
should be as close as possible
to the IC. Ensure accurate current sensing with Kelvin
connections at the SENSE resistor.
5. Is the INTV
CC
decoupling capacitor connected close
to the IC, between the INTV
CC
and the power ground
pins? This capacitor carries the MOSFET drivers current
peaks. An additionalF ceramic capacitor placed im-
mediately next to the INTV
CC
and PGND pins can help
improve noise performance substantially.
6. Keep the switching node (SW), top gate node (TG), and
boost node (BOOST) away from sensitive small-signal
nodes. All of these nodes have very large and fast moving
signals and therefore should be kept on theoutput side
of the LTC3835 and occupy minimum PC trace area.
7. Use a modifiedstar ground” technique: a low imped-
ance, large copper area central grounding point on
the same side of the PC board as the input and output
capacitors with tie-ins for the bottom of the INTV
CC
decoupling capacitor, the bottom of the voltage feedback
resistive divider and the SGND pin of the IC.
PC Board Layout Debugging
It is helpful to use a DC-50
MHz current probe to monitor
the current in the inductor while testing the circuit. Monitor
the output switching node (SW pin) to synchronize the
oscilloscope to the internal oscillator and probe the actual
output voltage as well. Check for proper performance
over the operating voltage and current range expected
in the application. The frequency of operation should be
maintained over the input voltage range down to dropout
and until the output load drops below the low current
operation thresholdtypically 10% of the maximum
designed current level in Burst Mode operation.
The duty cycle percentage should be maintained from cycle
to cycle in a well-designed, low noise PCB implementation.
Variation in the duty cycle at a subharmonic rate can sug-
gest noise pickup at the current or voltage sensing inputs
or inadequate loop compensation.
Overcompensation of
the loop can be used to tame a poor PC layout if regulator
bandwidth optimization is not required.
Reduce V
IN
from its nominal level to verify operation of
the regulator in dropout. Check the operation of the un-
dervoltage lockout circuit by further lowering V
IN
while
monitoring the outputs to verify operation.
Investigate whether any problems exist only at higher out-
put currents or
only at higher input voltages. If problems
coincide with high input voltages and low output currents,
look for capacitive coupling between the BOOST, SW, TG,
and possibly BG connections and the sensitive voltage
and current pins. The capacitor placed across the current
sensing pins needs to be placed immediately adjacent to
the pins of the IC. This capacitor helps to minimize the
effects of differential noise injection
due to high frequency
capacitive coupling. If problems are encountered with
high current output loading at lower input voltages, look
for inductive coupling between C
IN
, Schottky and the top
LTC3835
24
3835fe
For more information www.linear.com/LTC3835
APPLICATIONS INFORMATION
MOSFET components to the sensitive current and voltage
sensing traces. In addition, investigate common ground
path voltage pickup between these components and the
SGND pin of the IC.
An embarrassing problem, which can be missed in an
otherwise properly working switching regulator, results
when the current sensing leads are hooked up backwards.
The output voltage under this improper hookup will still
be maintained but the
advantages of current mode control
will not be realized. Compensation of the voltage loop will
be much more sensitive to component selection. This
behavior can be investigated by temporarily shorting out
the current sensing resistor—don’t worry, the regulator
will still maintain control of the output voltage.
Figure 9. LTC3835 Recommended Printed Circuit Layout Diagram
C1
1nF
C
B
D
B
M2
M1
C
IN
L1
C
OUT
V
OUT
V
IN
3835 F09
CLKOUT
PLLLPF
I
TH
TRACK/SS
V
FB
SGND
PGND
BG
INTV
CC
EXTV
CC
PHASMD
PLLIN/MODE
PGOOD
SENSE
+
SENSE
RUN
BOOST
TG
SW
V
IN
LTC3835EFE
D1
OPTIONAL
Figure 10. Branch Current Waveforms
R
L1
D1
L1
SW
R
SENSE
V
OUT
C
OUT
V
IN
C
IN
R
IN
BOLD LINES INDICATE HIGH SWITCHING
CURRENT. KEEP LINES TO A MINIMUM LENGTH.
3835 F10

LTC3835EUFD#PBF

Mfr. #:
Manufacturer:
Analog Devices / Linear Technology
Description:
Switching Voltage Regulators L IQ Sync Buck Cntr
Lifecycle:
New from this manufacturer.
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