LTC2351-12
13
235112fa
APPLICATIONS INFORMATION
SELECTING THE NUMBER OF CONVERTED CHANNELS
(SEL2, SEL1, SEL0)
These three control pins select the number of channels
being converted. 000 selects only the fi rst channel (CH0)
for conversion. Incrementing SELx selects additional
channels for conversion, up to 6 channels. 101, 110 or
111 select all 6 channels for conversion. These pins must
be kept in a fi xed state during conversion and during the
subsequent conversion to read data. When changing modes
between conversions, keep in mind that the output data
of a particular channel will remain unchanged until after
that channel is converted again. For example: convert
a sequence of 4 channels (CH0, CH1, CH2, CH3) with
SELx = 011, then, after these channels are converted
change SELx to 001 to convert just CH0 and CH1. See
Table 1. During the conversion of the fi rst set of two
channels you will be able to read the data from the same
two channels converted as part of the previous group
of 4 channels. Later, you could convert 4 or more chan-
nels to read back the unread CH2 and CH3 data that was
converted in the fi rst set of 4 channels. These pins are
often hardwired to enable the right number of channels
for a particular application. Choosing to convert fewer
channels per conversion results in faster throughput of
those channels. For example, 6 channels can be converted
at 250ksps/ch, while 3 channels can be converted at
500ksps/ch.
BIPOLAR/UNIPOLAR MODE
The input voltage range for each of the CHx input differ-
ential pairs is UNIPOLAR 0V – 2.5V when BIP is LOW, and
BIPOLAR ±1.25V when BIP is HIGH. This pin must be kept
in fi xed state during conversion and during subsequent
conversion to read data. When changing BIP between con-
versions the full acquisition time must be allowed before
starting the next conversion. After changing modes from
BIPOLAR to UNIPOLAR, or from UNIPOLAR to BIPOLAR,
you can still read the fi rst set of channels in the new mode,
by inverting the MSB to read these channels in the mode
that they were converted in.
DRIVING THE ANALOG INPUT
The differential analog inputs of the LTC2351-12 may be
driven differentially or as a single-ended input (i.e., the
CH0
input is grounded). All twelve analog inputs of all
six differential analog input pairs, CH0
+
and CH0
, CH1
+
and CH1
, CH2
+
and CH2
, CH3
+
and CH3
, CH4
+
and
CH4
and CH5
+
and CH5
, are sampled at the same in-
stant. Any unwanted signal that is common to both inputs
of each input pair will be reduced by the common mode
rejection of the sample-and-hold circuit. The inputs draw
only one small current spike while charging the sample-
and-hold capacitors at the end of conversion. During
conversion, the analog inputs draw only a small leakage
Table 1. Conversion Sequence Control
(“acquire” represents simultaneous sampling of all channels; CHx represents conversion of channels)
SEL2 SEL1 SEL0 CHANNEL ACQUISITION AND CONVERSION SEQUENCE
0 0 0 acquire, CH0, acquire, CH0...
0 0 1 acquire, CH0, CH1, acquire, CH0, CH1...
0 1 0 acquire, CH0, CH1, CH2, acquire, CH0, CH1, CH2...
0 1 1 acquire, CH0, CH1, CH2, CH3, acquire, CH0, CH1, CH2, CH3...
1 0 0 acquire, CH0, CH1, CH2, CH3, CH4, acquire, CH0,CH1,CH2, CH3, CH4...
1 0 1 acquire, CH0, CH1, CH2, CH3, CH4, CH5, acquire, CH0, CH1, CH2, CH3, CH4, CH5...
1 1 0 acquire, CH0, CH1, CH2, CH3, CH4, CH5, acquire, CH0, CH1, CH2, CH3, CH4, CH5...
1 1 1 acquire, CH0, CH1, CH2, CH3, CH4, CH5, acquire, CH0, CH1, CH2, CH3, CH4, CH5...
LTC2351-12
14
235112fa
APPLICATIONS INFORMATION
applications (to 1/3 Nyquist) where rail-to-rail performance
is desired. Quad version is available as LT1631.
LT1632: Dual 45MHz Rail-to-Rail Voltage FB Amplifi er.
2.7V to ±15V supplies. Very high A
VOL
, 1.5mV offset and
400ns settling to 0.5LSB for a 4V swing. It is suitable for
applications with a single 5V supply. THD and noise are
–93dB to 40kHz and below 1LSB to 800kHz (A
V
= 1,
2V
P-P
into 1kΩ, V
S
= 5V), making the part excellent for
AC applications where rail-to-rail performance is desired.
Quad version is available as LT1633.
LT1801: 80MHz GBWP, –75dBc at 500kHz, 2mA/amplifi er,
8.5nV/√Hz.
LT1806/LT1807: 325MHz GBWP, –80dBc distortion at
5MHz, unity gain stable, rail-to-rail in and out, 10mA/am-
plifi er, 3.5nV/√Hz.
LT1810: 180MHz GBWP, –90dBc distortion at 5MHz,
unity gain stable, rail-to-rail in and out, 15mA/amplifi er,
16nV/√Hz.
LT1818/LT1819: 400MHz, 2500V/μs, 9mA, Single/Dual
Voltage Mode Operational Amplifi er.
LT6200: 165MHz GBWP, –85dBc distortion at 1MHz,
unity gain stable, rail-to-rail in and out, 15mA/amplifi er,
0.95nV/√Hz.
LT6203: 100MHz GBWP, –80dBc distortion at 1MHz,
unity gain stable, rail-to-rail in and out, 3mA/amplifi er,
1.9nV/√Hz.
LT6600: Amplifi er/Filter Differential In/Out with 10MHz
Cutoff Frequency.
INPUT FILTERING AND SOURCE IMPEDANCE
The noise and the distortion of the input amplifi er and
other circuitry must be considered since they will add to
the LTC2351-12 noise and distortion. The small-signal
bandwidth of the sample-and-hold circuit is 50MHz. Any
noise or distortion products that are present at the analog
inputs will be summed over this entire bandwidth. Noisy
input circuitry should be fi ltered prior to the analog inputs.
A simple 1-pole RC fi lter is suffi cient for many applica-
tions. For example, Figure 1 shows a 47pF capacitor from
CHO
+
to ground and a 51Ω source resistor to limit the
current. If the source impedance of the driving circuit is
low, then the LTC2351-12 inputs can be driven directly. As
source impedance increases, so will acquisition time. For
minimum acquisition time with high source impedance,
a buffer amplifi er must be used. The main requirement is
that the amplifi er driving the analog input(s) must settle
after the small current spike before the next conversion
starts (the time allowed for settling must be at least 39ns
for full throughput rate). Also keep in mind while choos-
ing an input amplifi er the amount of noise and harmonic
distortion added by the amplifi er.
CHOOSING AN INPUT AMPLIFIER
Choosing an input amplifi er is easy if a few requirements
are taken into consideration. First, to limit the magnitude
of the voltage spike seen by the amplifi er from charging
the sampling capacitor, choose an amplifi er that has a low
output impedance (< 100Ω) at the closed-loop bandwidth
frequency. For example, if an amplifi er is used in a gain
of 1 and has a unity-gain bandwidth of 50MHz, then the
output impedance at 50MHz must be less than 100Ω.
The second requirement is that the closed-loop band-
width must be greater than 40MHz to ensure adequate
small-signal settling for full throughput rate. If slower op
amps are used, more time for settling can be provided by
increasing the time between conversions. The best choice
for an op amp to drive the LTC2351-12 depends on the
application. Generally, applications fall into two categories:
AC applications where dynamic specifi cations are most
critical and time domain applications where DC accuracy
and settling time are most critical. The following list is a
summary of the op amps that are suitable for driving the
LTC2351-12. (More detailed information is available in
the Linear Technology Databooks and on the website at
www.linear.com.)
LTC1566-1: Low Noise 2.3MHz Continuous Time
Lowpass Filter.
LT
®
1630: Dual 30MHz Rail-to-Rail Voltage FB Amplifi er.
2.7V to ±15V supplies. Very high A
VOL
, 500μV offset and
520ns settling to 0.5LSB for a 4V swing. THD and noise
are –93dB to 40kHz and below 1LSB to 320kHz (A
V
= 1,
2V
P-P
into 1kΩ, V
S
= 5V), making the part excellent for AC
LTC2351-12
15
235112fa
LTC2351-12
V
REF
GND
235112 F02
23
22
10μF
LT1790-3
3.5V TO 18V
LTC2351-12
CH0
+
CH0
V
REF
GND
235112 F01
1
2
11
3
10μF
47pF*
51Ω*
CH1
+
CH1
4
5
47pF*
*TIGHT TOLERANCE REQUIRED TO AVOID
APERTURE SKEW DEGRADATION
51Ω*
ANALOG
INPUT
ANALOG
INPUT
APPLICATIONS INFORMATION
INTERNAL REFERENCE
The LTC2351-12 has an on-chip, temperature compen-
sated, bandgap reference that is factory trimmed to 2.5V
to obtain a precise 2.5V input span. The reference amplifi er
output V
REF
, (Pin 23) must be bypassed with a capacitor
to ground. The reference amplifi er is stable with capaci-
tors of 1μF or greater. For the best noise performance, a
10μF ceramic or a 10μF tantalum in parallel with a 0.1μF
ceramic is recommended. The V
REF
pin can be overdriven
with an external reference as shown in Figure 2. The
voltage of the external reference must be higher than the
2.5V of the open-drain P-channel output of the internal
reference. The recommended range for an external refer-
ence is 2.55V to V
DD
. An external reference at 2.55V will
see a DC quiescent load of 0.75mA and as much as 3mA
during conversion.
Figure 1. RC Input Filter
Figure 2. Overdriving V
REF
Pin with an External Reference
net input bandwidth to 30MHz. The 47pF capacitor also
acts as a charge reservoir for the input sample-and-hold
and isolates the ADC input from sampling-glitch sensitive
circuitry. High quality capacitors and resistors should be
used since these components can add distortion. NPO
and silvermica type dielectric capacitors have excellent
linearity. Carbon surface mount resistors can generate
distortion from self heating and from damage that may
occur during soldering. Metal fi lm surface mount resistors
are much less susceptible to both problems. When high
amplitude unwanted signals are close in frequency to the de-
sired signal frequency a multiple pole fi lter is required.
High external source resistance, combined with 13pF
of input capacitance, will reduce the rated 50MHz input
bandwidth and increase acquisition time beyond 39ns.
INPUT RANGE
The analog inputs of the LTC2351-12 may be driven fully
differentially with a single supply. Either input may swing
up to V
CC
, provided the differential swing is no greater
than 2.5V with BIP (Pin 29) Low, or ±1.25V with (BIP Pin
29) High. The 0V to 2.5V range is also ideally suited for
single-ended input use with single supply applications. The
common mode range of the inputs extend from ground
to the supply voltage V
CC
. If the difference between the
CH
+
and CH
at any input pair exceeds 2.5V (unipolar) or
1.25V (bipolar), the output code will stay fi xed at positive
full-scale, and if this difference goes below 0V (unipolar)
or –1.25V (bipolar), the output code will stay fi xed at
negative full-scale.
INPUT SPAN VERSUS REFERENCE VOLTAGE
The differential input range has a unipolar voltage span
that equals the difference between the voltage at the
reference buffer output V
REF
(Pin 23) and the voltage at
ground. The differential input range of the ADC is 0V to
2.5V when using the internal reference. The internal ADC
is referenced to these two nodes. This relationship also
holds true with an external reference.
DIFFERENTIAL INPUTS
The ADC will always convert the difference of CH
+
minus
CH
, independent of the common mode voltage at any pair
of inputs. The common mode rejection holds up at high
frequencies (see Figure 3.) The only requirement is that
both inputs not go below ground or exceed V
DD
.

LTC2351CUH-12#TRPBF

Mfr. #:
Manufacturer:
Analog Devices Inc.
Description:
Analog to Digital Converters - ADC 12-Bit, 6-Channel 1.5Msps Simultaneous Samping ADC
Lifecycle:
New from this manufacturer.
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