LT4180
7
4180fb
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operaTion
Voltage drops in wiring can produce considerable load
regulation errors in electrical systems (Figure 1). As
load current, I
L
, increases the voltage drop in the wiring
(I
L
RW) increases and the voltage delivered to the sys-
tem (V
L
) drops. The traditional approach to solving this
problem, remote sensing, regulates the voltage at the load,
increasing the power supply voltage (V
OUT
) to compensate
for voltage drops in the wiring. While remote sensing
works well, it does require an additional pair of wires to
measure at the load, which may not always be practical.
The LT4180 eliminates the need for a pair of remote sense
wires by creating a Virtual Remote Sense. Virtual remote
sensing is achieved by measuring the incremental change
in voltage that occurs with an incremental change in current
in the wiring (Figure 2). This measurement can then be
used to infer the total DC voltage drop in the wiring, which
can then be compensated for. The Virtual Remote Sense
takes over control of the power supply via the feedback
pin (V
FB
) of the power supply maintaining tight regulation
of load voltage, V
L
.
The LT4180 operates by modulating the output current of
the regulator and looking at the resulting voltage change.
A
large output capacitor is placed across the load so the
AC impedance at the load is low.
[Normally, a capacitor
appears across the load in remote sensing situations to
keep the impedance low at that point].
This capacitor is
large enough that the AC impedance at the load is very low
compared to the line resistance. When the output current
is modulated, any voltage change that appears across the
terminals of the LT4180 is due to the resistance in the line
since the AC resistance at the load is very low.
There are four sample-and-hold capacitors in the LT4180.
The operation cycles through several stages to obtain the
correction voltage. First, the output voltage is regulated
and the control point is sampled and held. The control
loop is then switched to a current regulating control loop
and the output current is changed by 10%. Tw o sample-
and-hold currents store the voltage at the high current and
low current level of the modulation. This voltage change
is the result of a 10% change in current, making the volt-
age change 10% of the total drop in the line. The voltage
change
is amplified by a factor of 10.
The amplified voltage change that occurs with the current
is again sampled and held and is used as the correction
voltage. The correction voltage is summed into the output
and this corrects for the line drop. Since this correction
is actually open-loop, the actual voltage at the load is not
measured. The ability of the LT4180 to correct for line
drops is dependent upon the accuracy of the computations.
The LT4180 can correct better than 50 to 1 for line drops.
For example, a 10V drop in the line becomes a 200mV
change at the load.
The frequency of the correction cycle can be set from over
32kHz down to less than 250Hz, depending on the size of
the capacitors in the system. For very large capacitors in
high current systems, the dither correction clock would be
run more slowly. In simpler systems with smaller output
capacitors, the dither can be run at a higher frequency. If
the load contains frequencies similar to the dither, beat
notes can result between the load and the LT4180. A
spread spectrum option on the LT4180 allows the device
to change phasing during the correction cycle
so that it
will not inter
fere with load pulses.
Finally, the LT4180 takes into account all resistances
between the LT4180 and the load capacitor. It can correct
for cable connections, line resistances and varying contact
resistances. By measuring the peak change at the output of
the LT4180 one can monitor the impedance between the
LT4180 and the load, and detect increasing impedances
Figure 1. Traditional Remote Sensing Figure 2. Virtual Remote Sensing
4180 F02
POWER WIRING
I
L
VIRTUAL REMOTE
SENSE
POWER SUPPLY
+
RW
V
OUT
V
FB
SYSTEM
+
V
L
4180 F01
POWER WIRING
I
L
REMOTE SENSE WIRING
POWER SUPPLY
+
RW
V
OUT
SYSTEM
+
V
L
LT4180
8
4180fb
For more information www.linear.com/4180
INTRODUCTION
The LT4180 is designed to interface with a variety of power
supplies and regulators having either an external feedback
or control pin. In Figure 4, the regulator error amplifier
(which is a g
m
amplifier) is disabled by tying its inverting
input to ground. This converts the error amplifier into a
constant-current source which is then controlled by the
drain pin of the LT4180. This is the preferred method of
interfacing because it eliminates the regulator error ampli-
fier from the control loop which simplifies compensation
and provides best control loop response.
applicaTions inForMaTion
Figure 4. Nonisolated Regulator Interface
For proper operation, increasing control voltage should
correspond to increasing regulator output. For example,
in the case of a current mode switching power supply,
the control pin ITH should produce higher peak currents
as the ITH pin voltage is made more positive.
Figure 5. Isolated Power Supply Interface
Figure 6. Cascoded DRAIN Pin for Isolated Supplies
DRAIN
4180 F04
LT4180
I
TH
OR
V
C
REGULATOR
+
DRAIN
4180 F05
LT4180
V
C
INTV
CC
REGULATOR
OPTO-COUPLER
+
DRAIN
4180 F06
INTV
CC
LT4180
TO V
C
> 5V
COMP
from degrading contacts. Making the capacitor larger can
minimize the voltage ripple at the load due to a combination
of load regulation and the dither frequency of the LT4180.
Figure 3 shows the timing diagram for Virtual Remote
Sense. A new cycle begins when the power supply and
Virtual Remote Sense close the loop around V
OUT
(regulate
V
OUT
= H). Both V
OUT
and I
OUT
slew and settle to a new
value, and these values are stored in the Virtual Remote
Sense (track V
OUT
high = L and track I
OUT
= L). The V
OUT
feedback loop is opened and a new feedback loop is set
up commanding the power supply to deliver 90% of the
previously measured current (0.9I
OUT
). V
OUT
drops to a new
value as the power supply reaches a new steady state, and
this information is also stored in the Virtual Remote Sense.
At this point, the change in output voltage (∆V
OUT
) for a
Figure 3. Simplified Timing Diagram, Virtual Remote Sense
V
OUT
TRACK ∆V
OUT
REGULATE V
OUT
TRACK V
OUT
HIGH
TRACK I
OUT
REGULATE I
OUT
LOW
TRACK V
OUT
LOW
4180 F03
Isolated power supplies and regulators may also be used
by adding an opto-coupler (Figure 5). LT4180 output volt-
age INTV
CC
supplies power to the opto-coupler LED. In
situations where the control pin V
C
of the regulator may
exceed 5V, a cascode may be added to keep the DRAIN
pin of the LT4180 below 5V (Figure 6). Use a low VT
MOSFET for the cascode transistor.
–10% change in output current has been measured and
is stored in the Virtual Remote Sense. This voltage is used
during the next Virtual Remote Sense cycle to compensate
for voltage drops due to wiring resistance.
operaTion
LT4180
9
4180fb
For more information www.linear.com/4180
applicaTions inForMaTion
DESIGN PROCEDURE
The first step in the design procedure is to determine
whether the LT4180 will control a linear or switching supply/
regulator. If using a switching power supply or regulator,
it is recommended that the supply be synchronized to the
LT4180 by connecting the OSC pin to the SYNC pin (or
equivalent) of the supply.
If the power supply is synchronized to the LT4180, the
power supply switching frequency is determined by:
f
OSC
=
4
R
OSC
C
OSC
Recommended values for R
OSC
are between 20k and 100k
(with 30.1k the optimum for best accuracy) and greater
than 100pF for C
OSC
. C
OSC
may be reduced to as low as
50pF, but oscillator frequency accuracy will be somewhat
degraded.
The following example synchronizes a 250kHz switching
power supply to the LT4180. In this example, start with
R
OSC
= 30.1k:
C
OSC
=
4
250kHz 30.1k
= 531pF
This example uses 470pF. For 250kHz:
R
OSC
=
4
250kHz 470pF
= 34.04k
The closest standard 1% value is 34k.
The next step is to determine the highest practical dither
frequency. This may be limited either by the response
time of the power supply or regulator, or by the propaga-
tion time of the wiring connecting the load to the power
supply or regulator.
First determine the settling time (to 1% of final value)
of the power supply. The settling time should be the
worst-case value (over the whole operating envelope: V
IN
,
I
LOAD
, etc.).
F1 =
1
2 t
SETTLING
Hz
For example, if the power supply takes 1ms to settle
(worst-case) to within 1% of final value:
F1 =
2 1e 3
= 500Hz
Next, determine the propagation time of the wiring. In
order to ignore transmission line effects, the dither period
should be approximately twenty times longer than this.
This will limit dither frequency to:
F2 =
V
F
20 1.017ns/ft L
Hz
Where V
F
is the velocity factor (or velocity of propagation),
and L is the length of the wiring (in feet).
For example, assume the load is connected to a power
supply with 1000ft of CAT5 cable. Nominal velocity of
propagation is approximately 70%.
F2 =
0.7
20 1.017e 9 1000
= 34.4kHz
The maximum dither frequency should not exceed F1 or
F2 (whichever is less):
f
DITHER
< min (F1, F2).
Continuing this example, the dither frequency should be
less than 500Hz (limited by the power supply).
With the dither frequency known, the division ratio can
be determined:
D
RATIO
=
f
OSC
f
DITHER
=
250,000
500
= 500
The nearest division ratio is 512 (set DIV0 = L, DIV1 =
DIV2 = H). Based on this division ratio, nominal dither
frequency will be:
f
DITHER
=
f
OSC
D
RATIO
=
250,000
512
= 488Hz
After the dither frequency is determined, the minimum
load decoupling capacitor can be determined. This load
capacitor must be sufficiently large to filter out the dither
signal at the load.

LT4180EGN#TRPBF

Mfr. #:
Manufacturer:
Analog Devices / Linear Technology
Description:
Power Management Specialized - PMIC Virtual Remote Sense Cntr
Lifecycle:
New from this manufacturer.
Delivery:
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