4
LT3436
3436fa
TYPICAL PERFOR A CE CHARACTERISTICS
UW
GND (Pins 1, 5, 6, 8, 9, 16, 17): Short GND pins 1, 5, 6,8,
9, 16 and the exposed pad (pin 17) on the PCB. The GND
is the reference for the regulated output, so load regulation
will suffer if the “ground” end of the load is not at the same
voltage as the GND of the IC. This condition occurs when
the load current flows through the metal path between the
GND pins and the load ground point. Keep the ground path
short between the GND pins and the load and use a ground
plane when possible. Keep the path between the input
bypass and the GND pins short. The exposed pad should
be attached to a large copper area to improve thermal
performance.
V
IN
(Pin 2): This pin powers the internal circuitry and
internal regulator. Keep the external bypass capacitor
close to this pin.
SW (Pins 3, 4): The switch pin is the collector of the on-
chip power NPN switch and has large currents flowing
through it. Keep the traces to the switching components as
short as possible to minimize radiation and voltage spikes.
SHDN (Pin 11): The shutdown pin is used to turn off the
regulator and to reduce input drain current to a few
microamperes. The 1.35V threshold can function as an
accurate undervoltage lockout (UVLO), preventing the
regulator from operating until the input voltage has reached
a predetermined level. Float or pull high to put the regula-
tor in the operating mode.
FB (Pin 12): The feedback pin is used to set output voltage
using an external voltage divider that generates 1.2V at the
pin with the desired output voltage. If required, the current
limit can be reduced during start up when the FB pin is
below 0.5V (see the Current Limit Foldback graph in the
Typical Performance Characteristics section). An imped-
ance of less than 5k at the FB pin is needed for this
feature to operate.
V
C
(Pin 13): The V
C
pin is the output of the error amplifier
and the input of the peak switch current comparator. It is
normally used for frequency compensation, but can do
double duty as a current clamp or control loop override.
This pin sits at about 0.3V for very light loads and 0.9V at
maximum load.
SYNC (Pin 14): The sync pin is used to synchronize the
internal oscillator to an external signal. It is directly logic
compatible and can be driven with any signal between
20% and 80% duty cycle. The synchronizing range is
equal to
initial
operating frequency, up to 1.4MHz. See
Synchronization section in Applications Information for
details. When not in use, this pin should be grounded.
SHDN Supply Current Input Supply Current
Current Limit Foldback
PIN FUNCTIONS
UUU
SHDN VOLTAGE (V)
0
V
IN
CURRENT (µA)
300
250
200
150
100
50
0
0.6 1.0
3436 G07
0.2 0.4
0.8 1.2 1.4
INPUT VOLTAGE (V)
0
V
IN
CURRENT (µA)
1200
1000
800
600
400
200
0
5
10 15 20
3436 G08
25 30
FEEDBACK VOLTAGE (V)
0 0.2
SWITCH PEAK CURRENT (A)
0.4 0.80.6
1.0
1.2
3436 G09
4.0
3.5
3.0
2.5
2.0
1.5
1.0
0.5
0
FB INPUT CURRENT (µA)
40
30
20
10
0
T
A
= 25°C
V
IN
= 15V
T
A
= 25°C
T
A
= 25°C
MINIMUM
INPUT
VOLTAGE
SWITCH CURRENT
5
LT3436
3436fa
amplifier commands current to be delivered to the output
rather than voltage. A voltage fed system will have low
phase shift up to the resonant frequency of the inductor
and output capacitor, then an abrupt 180° shift will occur.
The current fed system will have 90° phase shift at a much
lower frequency, but will not have the additional 90° shift
until well beyond the LC resonant frequency. This makes
it much easier to frequency compensate the feedback loop
and also gives much quicker transient response.
A comparator connected to the shutdown pin disables the
internal regulator, reducing supply current.
The LT3436 is a constant frequency, current-mode boost
converter. This means that there is an internal clock and
two feedback loops that control the duty cycle of the power
switch. In addition to the normal error amplifier, there is a
current sense amplifier that monitors switch current on a
cycle-by-cycle basis. A switch cycle starts with an oscilla-
tor pulse which sets the R
S
flip-flop to turn the switch on.
When switch current reaches a level set by the inverting
input of the comparator, the flip-flop is reset and the
switch turns off. Output voltage control is obtained by
using the output of the error amplifier to set the switch
current trip point. This technique means that the error
Figure 1. Block Diagram
BLOCK DIAGRAM
W
+
+
Σ
INPUT
2.5V BIAS
REGULATOR
800kHz
OSCILLATOR
SW
FB
V
C
GND
3436 F01
SLOPE COMP
0.005
INTERNAL
V
CC
CURRENT SENSE
AMPLIFIER VOLTAGE
GAIN = 40
SYNC
SHDN
SHUTDOWN
COMPARATOR
CURRENT
COMPARATOR
ERROR
AMPLIFIER
g
m
= 850µMho
R
S
FLIP-FLOP
DRIVER
CIRCUITRY
S
R
0.3V
Q1
POWER
SWITCH
1.2V
+
+
1.35V
A
7µA
6
LT3436
3436fa
APPLICATIONS INFORMATION
WUU
U
FB RESISTOR NETWORK
The suggested resistance (R2) from FB to ground is 10k
1%. This reduces the contribution of FB input bias current
to output voltage to less than 0.2%. The formula for the
resistor (R1) from V
OUT
to FB is:
R
RV
RA
OUT
1
212
12 202
=
()
µ
.
.(.)
Figure 2. Feedback Network
OUTPUT CAPACITOR
Step-up regulators supply current to the output in pulses.
The rise and fall times of these pulses are very fast. The
output capacitor is required to reduce the voltage ripple
this causes. The RMS ripple current can be calculated
from:
IIVVV
RIPPLE RMS
OUT OUT IN IN
()
=
()
/
The LT3436 will operate with both ceramic and tantalum
output capacitors. Ceramic capacitors are generally cho-
sen for their small size, very low ESR (effective series
resistance), and good high frequency operation, reducing
output ripple voltage. Their low ESR removes a useful zero
in the loop frequency response, common to tantalum
capacitors. To compensate for this, the V
C
loop compen-
sation pole frequency must typically be reduced by a factor
of 10. Typical ceramic output capacitors are in the 4.7µF
+
1.2V
V
SW
V
C
GND
3436 F02
R1
R2
10k
OUTPUT
ERROR
AMPLIFIER
FB
LT3436
+
to 22µF range. Since the absolute value of capacitance
defines the pole frequency of the output stage, an X7R or
X5R type ceramic, which have good temperature stability,
is recommended.
Tantalum capacitors are usually chosen for their bulk
capacitance properties, useful in high transient load appli-
cations. ESR rather than absolute value defines output
ripple at 800kHz. Values in the 22µF to 100µF range are
generally needed to minimize ESR and meet ripple current
ratings. Care should be taken to ensure the ripple ratings
are not exceeded.
Table 1. Surface Mount Solid Tantalum Capacitor ESR and
Ripple Current
E Case Size ESR (Max,
) Ripple Current (A)
AVX TPS, Sprague 593D 0.1 to 0.3 0.7 to 1.1
D Case Size
AVX TPS, Sprague 593D 0.1 to 0.3 0.7 to 1.1
C Case Size
AVX TPS 0.2 (typ) 0.5 (typ)
INPUT CAPACITOR
Unlike the output capacitor, RMS ripple current in the
input capacitor is normally low enough that ripple current
rating is not an issue. The current waveform is triangular,
with an RMS value given by:
I
VV V
LfV
RIPPLE RMS
IN OUT IN
OUT
()
=
()
()
()()( )
029.
At higher switching frequency, the energy storage require-
ment of the input capacitor is reduced so values in the
range of 2.2µF to 10µF are suitable for most applications.
Y5V or similar type ceramics can be used since the
absolute value of capacitance is less important and has no
significant effect on loop stability. If operation is required
close to the minimum input voltage required by either the
output or the LT3436, a larger value may be necessary.
This is to prevent excessive ripple causing dips below the
minimum operating voltage resulting in erratic operation.

LT3436EFE#PBF

Mfr. #:
Manufacturer:
Analog Devices / Linear Technology
Description:
Switching Voltage Regulators 3A, 800kHz Boost Sw Reg
Lifecycle:
New from this manufacturer.
Delivery:
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