LTC3783
10
3783fb
OPERATION
The SS pin provides a soft-start current to charge an
external capacitor. Enabled by RUN, the soft-start current
is 50µA, which creates a positive voltage ramp on V
SS
to which the internal I
TH
is limited, avoiding high peak
currents on start-up. Once V
SS
reaches 1.23V, the full I
TH
range is established.
The LTC3783 can be used either by sensing the voltage
drop across the power MOSFET or by connecting the
SENSE pin to a conventional shunt resistor in the source
of the power MOSFET, as shown in the Typical Application
on the first page of this data sheet. Sensing the voltage
across the power MOSFET maximizes converter efficiency
and minimizes the component count, but limits the out-
put voltage to the maximum rating for this pin (36V). By
connecting the SENSE pin to a resistor in the source of
the power MOSFET, the user is able to program output
voltages significantly greater than 36V, limited only by
other components’ breakdown voltages.
Externally Synchronized Operation
When an external clock signal drives the SYNC pin at a
rate faster than the chip’s internal oscillator, the oscillator
will synchronize to it. When the oscillators internal logic
circuitry detects a synchronizing signal on the SYNC pin,
the internal oscillator ramp is terminated early and the
slope compensation is increased by approximately 25%.
As a result, in applications requiring synchronization, it
is recommended that the nominal operating frequency of
the IC be programmed to be about 80% of the external
clock frequency. Attempting to synchronize to too high
an external frequency (above 1.3f
OSC
) can result in inad-
equate slope compensation and possible subharmonic
oscillation (or jitter).
The external clock signal must exceed 2V for at least 25ns,
and should have a maximum duty cycle of 80%, as shown
in Figure 1. The MOSFET turn-on will synchronize to the
rising edge of the external clock signal.
Programming the Operating Frequency
The choice of operating frequency and inductor value is
a tradeoff between efficiency and component size. Low
frequency operation improves efficiency by reducing
MOSFET and diode switching losses. However, lower
frequency operation requires more inductance for a given
amount of load current.
The LTC3783 uses a constant frequency architecture that
can be programmed over a 20kHz to 1MHz range with
a single external resistor from the FREQ pin to ground,
as shown in the application on the first page of this data
sheet. The nominal voltage on the FREQ pin is 0.615V,
and the current that flows out of the FREQ pin is used to
charge and discharge an internal oscillator capacitor. The
oscillator frequency is trimmed to 300kHz with R
T
= 20k.
A graph for selecting the value of R
T
for a given operating
frequency is shown in Figure 2.
3783 F01
2V TO 7V
MODE/
SYNC
GATE
I
L
t
MIN
= 25ns
0.8T
D = 40%
T T = 1/f
O
Figure 1. MODE/SYNC Clock Input and Switching Waveforms
for Synchronized Operation
FREQUENCY (kHz)
10
R
T
(kΩ)
100
1 100 1000 10000
3783 G09
1
10
1000
Figure 2. Timing Resistor (R
T
) Value
LTC3783
11
3783fb
OPERATION
INTV
CC
Regulator Bypassing and Operation
An internal, P-channel low dropout voltage regulator pro-
duces the 7V supply which powers the gate drivers and
logic circuitry within the LTC3783 as shown in Figure 3.
The INTV
CC
regulator can supply up to 50mA and must be
bypassed to ground immediately adjacent to the IC pins
with a minimum of 4.7µF low ESR or ceramic capacitor.
Good bypassing is necessary to supply the high transient
currents required by the MOSFET gate driver.
For input voltages that don’t exceed 8V (the absolute
maximum rating for INTV
CC
is 9V), the internal low dropout
regulator in the LTC3783 is redundant and the INTV
CC
pin
can be shorted directly to the V
IN
pin. With the INTV
CC
pin shorted to V
IN
, however, the divider that programs the
regulated INTV
CC
voltage will draw 15µA from the input sup-
ply, even in shutdown mode. For applications that require
the lowest shutdown mode input supply current, do not
connect the INTV
CC
pin to V
IN
. Regardless of whether the
INTV
CC
pin is shorted to V
IN
or not, it is always necessary
to have the driver circuitry bypassed with a 4.7µF low ESR
ceramic capacitor to ground immediately adjacent to the
INTV
CC
and GND pins.
In an actual application, most of the IC supply current is
used to drive the gate capacitance of the power MOSFET.
As a result, high input voltage applications in which a
large power MOSFET is being driven at high frequencies
can cause the LTC3783 to exceed its maximum junction
temperature rating. The junction temperature can be
estimated using the following equations:
I
Q(TOT)
= I
Q
+ f • Q
G
P
IC
= V
IN
• (I
Q
+ f • Q
G
)
T
J
= T
A
+ P
IC
θ
JA
The total quiescent current I
Q(TOT)
consists of the static
supply current (I
Q
) and the current required to charge and
discharge the gate of the power MOSFET. The 16-lead FE
package has a thermal resistance of
θ
JA
= 38°C/W and
the DHD package has an
θ
JA
= 43°C/W
As an example, consider a power supply with V
IN
= 12V
and V
OUT
= 25V at I
OUT
= 1A. The switching frequency is
300kHz, and the maximum ambient temperature is 70°C.
The power MOSFET chosen is the Si7884DP, which has a
maximum R
DS(ON)
of 10mΩ (at room temperature) and
+
1.230V
R2 R1
P-CH
7V
DRIVER
GATE
C
VCC
4.7µF
X5R
C
IN
INPUT
SUPPLY
6V TO 36V
GND
PLACE AS CLOSE AS
POSSIBLE TO DEVICE PINS
M1
3783 F03
INTV
CC
V
IN
GND
LOGIC
6V-RATED
POWER
MOSFET
Figure 3. Bypassing the LDO Regulator and Gate Driver Supply
LTC3783
12
3783fb
OPERATION
a maximum total gate charge of 35nC (the temperature
coefficient of the gate charge is low).
I
Q(TOT)
= 1.2mA + 35nC • 300kHz = 12mA
P
IC
= 12V • 12mA = 144mW
T
J
= 70°C + 110°C/W • 144mW = 86°C
This demonstrates how significant the gate charge current
can be when compared to the static quiescent current in
the IC.
To prevent the maximum junction temperature from being
exceeded, the input supply current must be checked when
operating in a continuous mode at high V
IN
. A tradeoff
between the operating frequency and the size of the power
MOSFET may need to be made in order to maintain a reli-
able IC junction temperature. Prior to lowering the operat-
ing frequency, however, be sure to check with the power
MOSFET manufacturers for the latest low Q
G
, low R
DS(ON)
devices. Power MOSFET manufacturing technologies are
continually improving, with newer and better-performing
devices being introduced almost monthly.
Output Voltage Programming
In constant voltage mode, in order to regulate the output
voltage, the output voltage is set by a resistor divider ac-
cording to the following formula:
V
OUT
= V
FBP
1+
R2
R1
where 0 ≤ V
FBP
≤ 1.23V. The external resistor divider is
connected to the output as shown in Figure 4, allowing
remote voltage sensing. The resistors R1 and R2 are
typically chosen so that the error caused by the 500nA
input bias current flowing out of the FBN pin during
normal operation is less than 1%, which translates to
a maximum R1 value of about 25k at V
FBP
= 1.23V. For
lower FBP voltages, R1 must be reduced accordingly to
maintain accuracy, e.g., R1 < 2k for 1% accuracy when
V
FBP
= 100mV. More accuracy can be achieved with lower
resistances, at the expense of increased dissipation and
decreased light load efficiency.
A similar analysis applies to the V
FBP
resistive divider, if
one is used:
V
FBP
= V
REF
R3
R3
+
R4
where R3 is subject to a similar 500nA bias current.
LTC3783
R4
R3
RUN
PWMIN
I
TH
SS
V
REF
FBP
FBN
FREQ
SYNC
V
IN
OV/FB
PWMOUT
I
LIM
GATE
SENSE
INTV
CC
GND
V
IN
3V TO 36V
GND
V
OUT
R2
R1
3783 F04
Figure 4. LTC3783 Boost Application
Programming Turn-On and Turn-Off Thresholds
with the RUN Pin
The LTC3783 contains an independent, micropower voltage
reference and comparator detection circuit that remains
active even when the device is shut down, as shown in
Figure 5. This allows users to accurately program an input
voltage at which the converter will turn on and off. The
falling threshold on the RUN pin is equal to the internal
reference voltage of 1.248V. The comparator has 100mV
of hysteresis to increase noise immunity.
The turn-on and turn-off input voltage thresholds are
programed using a resistor divider according to the fol-
lowing formulas:
V
IN(OFF)
= 1.248V 1+
R2
R1
V
IN(ON)
= 1.348V 1+
R2
R1
The resistor R1 is typically chosen to be less than 1M.

LTC3783IFE#TRPBF

Mfr. #:
Manufacturer:
Analog Devices / Linear Technology
Description:
Switching Voltage Regulators PWM LED Drvr & Boost, Fly & SEPIC Conv
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