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With C
C
= 1µF, R
C
= 10k at V
IN
= 20V, V
BAT
= 7V, V
CSP
regulated at 9.8V and a 0.2A output load condition at
CSP, the transient response for a 100mA charge current
step observed at IBMON is shown in Figure 24.
The transient response now indicates an overall under
damped system. As noted in the empirical loop compensa-
tion section, the value of R
C
is now increased iteratively
until R
C
= 20k. The transient response of the same loop
with C
C
= 22nF and R
C
= 20k is shown in Figure 26.
Figure 24. Transient Response of Charge Current Regulation Loop
Observed at IBMON When V
OFB
is Regulated to V
OUT(INST_ON)
with
C
C
= 1µF, R
C
= 10k for a 100mA Charge Current Step
5ms/DIV
–20
V
IBMON
(mV)
5mV/DIV
15
–10
–5
0
5
10
–15
105 15
40001 F24
25200–10 –5–15
The transient response shows a small overshoot with slow
settling indicating a fast minor loop within a well damped
overall loop. Therefore, the value of C
C
is reduced iteratively
until C
C
=22nF. The transient response of the same loop
with C
C
= 22nF and R
C
= 10k is shown in Figure 25.
Figure 25. Transient Response of Charge Current Regulation Loop
Observed at IBMON When V
OFB
is Regulated to V
OUT(INST_ON)
with
C
C
= 22nF, R
C
= 10k for a 100mA Charge Current Step
Figure 26. Transient Response of Charge Current Regulation Loop
Observed at IBMON When V
OFB
is Regulated to V
OUT(INST_ON)
with
C
C
= 22nF, R
C
= 20k for a 100mA Charge Current Step
5ms/DIV
–20
V
IBMON
(mV)
5mV/DIV
15
–10
–5
0
5
10
–15
105 15
40001 F25
25200–10 –5–15
5ms/DIV
–20
V
IBMON
(mV)
5mV/DIV
15
–10
–5
0
5
10
–15
105 15
40001 F26
25200–10 –5–15
Note that the transient response is close to optimum
with some overshoot and fast settling. If after iteratively
increasing the value of R
C
, the transient response again
indicates an over damped system, the step of reducing
C
C
can be repeated. These steps of reducing C
C
followed
by increasing R
C
can be repeated continuously until one
arrives at a stable loop with the smallest value of C
C
and
the largest value of R
C
. In this particular example, these
values are found to be C
C
= 22nF and R
C
= 20kΩ.
After arriving at these final values of R
C
and C
C
, the stability
margin is checked by varying the values of both R
C
and
C
C
by 2:1 in all four possible combinations. After which
the setup condition is varied, including varying the input
voltage level and the output load level and the transient
response is checked at these different setup conditions.
Once the desired responses on all different conditions are
obtained, the values of R
C
and C
C
are noted.
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This same procedure is then repeated for the other four
loops: the input voltage regulation, the output voltage
regulation, the battery float voltage regulation and finally
the charge current regulation when V
OFB
> V
OUT(INST_ON)
.
Note that the resulting optimum values for each of the loops
may differ slightly. The final values of C
C
and R
C
are then
selected by combining the results and ensuring the most
conservative response for all the loops. This usually entails
picking the largest value of C
C
and the smallest value of
R
C
based on the results obtained for all the loops. In this
particular example, the value of C
C
is finally set to 47nF
and R
C
= 14.7kΩ.
BOARD LAYOUT CONSIDERATIONS
In the majority of applications, the most important param-
eter of the system is the battery float voltage. Therefore,
the user needs to be extra careful when placing and rout-
ing the feedback resistor R
BFB1
and R
BFB2
. In particular,
the battery sense line connected to R
BFB1
and the ground
return line for the LTC4000-1 must be Kelvined back
to where the battery output and the battery ground are
located respectively. Figure 27 shows this
Kelvin sense
configuration.
For accurate current sensing, the sense lines from R
IS
and R
CS
(Figure 27) must be Kelvined back all the way
to the sense resistors terminals. The two sense lines of
each resistor must also be routed close together and away
from noise sources to minimize error. Furthermore, cur-
rent filtering capacitors should be placed strategically to
ensure that very little AC current is flowing through these
sense resistors as mentioned in the applications section.
The decoupling capacitors C
IN
and C
BIAS
must be placed as
close to the LTC4000-1 as possible. This allows as short
a route as possible from C
IN
to the IN and GND pins, as
well as from C
BIAS
to the BIAS and GND pins.
In a typical application, the LTC4000-1 is paired with an
external DC/DC converter. The operation of this converter
often involves high dV/dt switching voltage as well as
high currents. Isolate these switching voltages and cur-
rents from the LTC4000-1 section of the board as much
as possible by using good board layout practices. These
include separating noisy power and signal grounds, having
a good low impedance ground plane, shielding whenever
necessary, and routing sensitive signals
as short as pos-
sible and away from noisy sections of the board.
Figure 27. Kelvin Sense Lines Configuration for LTC4000-1
40001 F27
V
IN
CSN
CLN
IN
CSP
BAT
GND
LTC4000-1
R
C
ITHGND
SWITCHING
CONVERTER
BGATE
ITH
IIDCC
C
C
IGATE
R
BFB1
R
IS
R
CS
R
BFB2
BFB
FBG
SYSTEM LOAD
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APPENDIX—THE LOOP TRANSFER FUNCTIONS
When a series resistor (R
C
) and capacitor (C
C
) is used
as the compensation network as shown in Figure 19, the
transfer function from the input of A4-A7 to the ITH pin
is simply as follows:
V
ITH
V
FB
(s)= g
m4-7
R
C
1
g
m10
C
C
s+1
R
O4-7
C
C
s
where g
m4-7
is the transconductance of error amplifier A4-
A7, typically 0.5mA/V; g
m10
is the output amplifier (A10)
transconductance, R
O4-7
is the output impedance of the
error amplifier, typically 50MΩ; and R
O10
is the effective
output impedance of the output amplifier, typically 10
with the ITH pin open circuit.
Note this simplification is valid when g
m10
R
O10
R
O4-7
C
C
= A
V10
R
O4-7
C
C
is much larger than any other
poles or zeroes in the system. Typically A
V10
R
O4-7
= 5
10
10
with the ITH pin open circuit. The exact value of g
m10
and R
O10
depends on the pull-up current and impedance
connected to the ITH pin respectively.
In most applications, compensation of the loops involves
picking the right values of R
C
and C
C
. Aside from picking
the values of R
C
and C
C
, the value of g
m10
may also be
adjusted. The value of g
m10
can be adjusted higher by
increasing the pull-up current into the ITH pin and its
value can be approximated as:
g
m10
=
I
ITH
+ 5µA
50mV
The higher the value of g
m10
, the smaller the lower limit
of the value of R
C
would be. This lower limit is to prevent
the presence of the right half plane zero.
Even though all the loops share this transfer function from
the error amplifier input to the ITH pin, each of the loops
has a slightly different dynamic due to differences in the
feedback signal path.
The Input Voltage Regulation Loop
The feedback signal for the input voltage regulation loop
is the voltage on the IFB pin, which is connected to the
center node of the resistor divider between the input
voltage (connected to the IN pin) and GND. This voltage
is compared to an internal reference (1.000V typical) by
the transconductance error amplifier A4. This amplifier
then drives the output transconductance amplifier (A10)
to appropriately adjust the voltage on the ITH pin driving
the external DC/DC converter to regulate the output volt-
age observed by the IFB pin. This loop is shown in detail
in Figure 28.
Assuming R
IS
<< R
IN
<< (R
IFB1
+ R
IFB2
), the simplified
loop transmission is as follows:
L
IV
(s) = g
m4
R
C
1
g
m10
C
C
s +1
C
C
s
Gmi
p
(s)
R
IN
R
IN
C
IN
+C
CLN
( )
s +1
R
IFB2
R
IFB
where Gmi
p
(s) is the transfer function from V
ITH
to the
input current of the external DC/DC converter, R
IN
is the
equivalent output impedance of the input source, and
R
IFB
= R
IFB1
+ R
IFB2
.
Figure 28. Simplified Linear Model of the Input Voltage
Regulation Loop
IN
CC
1V
ITH
LTC4000-1
IN CLN
R
IS
DC/DC INPUT
C
CLN
(OPTIONAL)
IFB
C
IN
+
+
C
C
TO DC/DC
40001 F28
R
C
R
IFB2
R
IFB1
A4
g
m4
= 0.5m
A10
g
m10
= 0.1m
R
O4
R
O10

LTC4000IUFD-1#TRPBF

Mfr. #:
Manufacturer:
Analog Devices / Linear Technology
Description:
Battery Management High Voltage, High Current Controller for Battery Charging and Power Management
Lifecycle:
New from this manufacturer.
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