LTC3728L/LTC3728LX
19
3728lxff
applicaTions inForMaTion
current ratings are often based on only 2000 hours of life.
This makes it advisable to further derate the capacitor, or
to choose a capacitor rated at a higher temperature than
required. Several capacitors may also be paralleled to meet
size or height requirements in the design. Always consult
the manufacturer if there is any question.
The benefit of the LTC3728L/LTC3728LX multiphase clock-
ing can be calculated by using the equation above for the
higher power controller and then calculating the loss that
would have resulted if both controller channels switched
on at the same time. The total RMS power lost is lower
when both controllers are operating due to the interleav-
ing of current pulses through the input capacitors ESR.
This is why the input capacitors requirement calculated
in the previous equation for the worst-case controller is
adequate for the dual controller design. Remember that
input protection fuse resistance, battery resistance and
PC board trace resistance losses are also reduced due to
the reduced peak currents in a multiphase system.
The
overall benefit of a multiphase design will only be fully
realized when the source impedance of the power supply/
battery is included in the efficiency testing.
The drains of
the two top MOSFETs should be placed within 1cm of each
other and share a common C
IN
(s). Separating the drains
and C
IN
may produce undesirable voltage and current
resonances at V
IN
.
The selection of C
OUT
is driven by the required effective
series resistance (ESR). Typically once the ESR require-
ment is satisfied the capacitance is adequate for filtering.
The output ripple (ΔV
OUT
) is determined by:
V
OUT
I
L
ESR +
1
8fC
OUT
Where f = operating frequency, C
OUT
= output capacitance,
and ΔI
L
= ripple current in the inductor. The output ripple
is highest at maximum input voltage since ΔI
L
increases
with input voltage. With ΔI
L
= 0.3I
OUT(MAX)
the output
ripple will typically be less than 50mV at the maximum
V
IN
assuming:
C
OUT
Recommended ESR < 2 R
SENSE
and C
OUT
> 1/(8fR
SENSE
)
The first condition relates to the ripple current into the ESR
of the output capacitance while the second term guarantees
that the output capacitance does not significantly discharge
during the operating frequency period due to ripple current.
The choice of using smaller output capacitance increases
the ripple voltage due to the discharging term but can be
compensated for by using capacitors of very low ESR to
maintain the ripple voltage at or below 50mV. The I
TH
pin
OPTI-LOOP compensation components can be optimized
to provide stable, high performance transient response
regardless of the output capacitors selected.
Manufacturers such as Nichicon, United Chemi-Con and
Sanyo can be considered for high performance through-
hole capacitors. The OS-CON semiconductor dielectric
capacitor available from Sanyo has the lowest (ESR)
(size) product of any aluminum electrolytic at a somewhat
higher price. An additional ceramic capacitor in parallel
with OS-CON capacitors is recommended to reduce the
inductance effects.
In surface mount applications, multiple capacitors may
need to be used in parallel to meet ESR, RMS cur-
rent handling and load step requirements. Aluminum
electrolytic, dry tantalum and special polymer capaci-
tors are available in surface mount packages. Special
polymer surface mount capacitors offer very low ESR
but have lower storage capacity per unit volume than
other capacitor types. These capacitors offer a very
cost-effective output capacitor solution and are an ideal
choice when combined with a controller having high
loop bandwidth. Tantalum capacitors offer the highest
capacitance density and are often used as output capaci-
tors for switching regulators having controlled soft-start.
Several excellent surge-tested choices are the AVX TPS,
AVX TPSV or the KEMET T510 series of surface mount
tantalums, available in case heights ranging from 2mm
to 4mm. Aluminum electrolytic capacitors can be used
in cost-driven applications providing that consideration
is given to ripple current ratings, temperature and long
term reliability. A typical application will require several
to many aluminum electrolytic capacitors in parallel. A
combination of the aforementioned capacitors will often
result in maximizing performance and minimizing overall
cost. Other capacitor types include Nichicon PL series,
LTC3728L/LTC3728LX
20
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applicaTions inForMaTion
Panasonic SP, NEC Neocap, Cornell Dubilier ESRE and
Sprague 595D series. Consult manufacturers for other
specific recommendations.
INTV
CC
Regulator
An internal P-channel low dropout regulator produces
5V at the INTV
CC
pin from the V
IN
supply pin. INTV
CC
powers the drivers and internal circuitry within the IC.
The INTV
CC
pin regulator can supply a peak current of
50mA and must be bypassed to ground with a minimum
of 4.7µF tantalum, 10µF special polymer, or low ESR type
electrolytic capacitor. A 1µF ceramic capacitor placed di-
rectly adjacent to the INTV
CC
and PGND IC pins is highly
recommended. Good bypassing is necessary to supply
the high transient currents required by the MOSFET gate
drivers and to prevent interaction between channels.
Higher input voltage applications in which large MOSFETs
are being driven at high frequencies may cause the maxi-
mum junction temperature rating for the IC to be exceeded.
The system supply current is normally dominated by the
gate charge current. Additional external loading of the
INTV
CC
and 3.3V linear regulators also needs to be taken
into account for the power dissipation calculations. The
total INTV
CC
current can be supplied by either the 5V in-
ternal linear regulator or by the EXTV
CC
input pin. When
the voltage applied to the EXTV
CC
pin is less than 4.7V, all
of the INTV
CC
current is supplied by the internal 5V linear
regulator. Power dissipation for the IC in this case is high-
est: (V
IN
)(I
INTVCC
), and overall efficiency is lowered. The
gate charge current is dependent on operating frequency
as discussed in the Efficiency Considerations section.
The junction temperature can be estimated by using the
equations given in Note 2 of the Electrical Characteristics.
For example, the IC V
IN
current is thermally limited to less
than 67mA from a 24V supply when not using the EXTV
CC
pin as follows:
T
J
= 70°C + (67mA)(24V)(34°C/W) = 125°C
Use of the EXTV
CC
input pin reduces the junction tem-
perature to:
T
J
= 70°C + (67mA)(5V)(34°C/W) = 81°C
The absolute maximum rating for the INTV
CC
pin is 40mA.
Dissipation should be calculated to also include any added
current drawn from the internal 3.3V linear regulator. To
prevent maximum junction temperature from being ex-
ceeded, the input supply current must be checked operating
in continuous mode at maximum V
IN
.
EXTV
CC
Connection
The IC contains an internal P-channel MOSFET switch
connected between the EXTV
CC
and INTV
CC
pins. When
the voltage applied to EXTV
CC
rises above
4.7V, the internal
regulator is turned off and the switch closes, connecting
the EXTV
CC
pin to the INTV
CC
pin, thereby supplying internal
power. The switch remains closed as long as the voltage
applied to EXTV
CC
remains above 4.5V. This allows the
MOSFET driver and control power to be derived from the
output during normal operation (4.7V < V
OUT
< 7V) and
from the internal regulator when the output is out of regu-
lation (start-up, short-circuit). If more current is required
through the EXTV
CC
switch than is specified, an external
Schottky diode can be added between the EXTV
CC
and
INTV
CC
pins. Do not apply greater than 7V to the EXTV
CC
pin and ensure that EXTV
CC
< V
IN
.
Significant efficiency gains can be realized by powering
INTV
CC
from the output, since the V
IN
current resulting
from the driver and control currents will be scaled by a
factor of (Duty Cycle)/(Efficiency). For 5V regulators this
supply means connecting the EXTV
CC
pin directly to V
OUT
.
However, for 3.3V and other lower voltage regulators,
additional circuitry is required to derive INTV
CC
power
from the output.
The following list summarizes the four possible connec-
tions for EXTV
CC
:
1. EXTV
CC
Left Open (or Grounded). This will cause
INTV
CC
to be powered from the internal 5V regulator
resulting in an efficiency penalty of up to 10% at high
input voltages.
2. EXTV
CC
Connected Directly to V
OUT
. This is the normal
connection for a 5V regulator and provides the highest
efficiency.
3. EXTV
CC
Connected to an External Supply. If an external
supply is available in the 5V to 7V range, it may be used
to power EXTV
CC
providing it is compatible with the
MOSFET gate drive requirements.
LTC3728L/LTC3728LX
21
3728lxff
applicaTions inForMaTion
4. EXTV
CC
Connected to an Output-Derived Boost Network.
For 3.3V and other low voltage regulators, efficiency
gains can still be realized by connecting EXTV
CC
to an
output-derived voltage that has been boosted to greater
than 4.7V. This can be done with either the inductive
boost winding as shown in Figure 6a or the capacitive
charge pump shown in Figure 6b. The charge pump has
the advantage of simple magnetics.
Topside MOSFET Driver Supply (C
B
, D
B
)
External bootstrap capacitors C
B
connected to the BOOST
pins supply the gate drive voltages for the topside MOS-
FETs. Capacitor C
B
in the Functional Diagram is charged
though external diode D
B
from INTV
CC
when the SW pin
is low. When one of the topside MOSFETs is to be turned
on, the driver places the C
B
voltage across the gate-source
of the desired MOSFET. This enhances the MOSFET and
turns on the topside switch. The switch node voltage, SW,
rises to V
IN
and the BOOST pin follows. With the topside
MOSFET on, the boost voltage is above the input supply:
V
BOOST
= V
IN
+ V
INTVCC
. The value of the boost capacitor
C
B
needs to be 100 times that of the total input capacitance
of the topside MOSFET(s). The reverse breakdown of the
external Schottky diode must be greater than V
IN(MAX)
.
When adjusting the gate drive level, the final arbiter is the
total input current for the regulator. If a change is made
and the input current decreases, then the efficiency has
improved. If there is no change in input current, then there
is no change in efficiency.
Output Voltage
The output voltages are each set by an external feedback
resistive divider carefully placed across the output capaci-
tor. The resultant feedback signal is compared with the
internal precision 0.800V voltage reference by the error
amplifier. The output voltage is given by the equation:
V
OUT
= 0.8V 1+
R2
R1
where R1 and R2 are defined in Figure 2.
SENSE
+
/SENSE
Pins
The common mode input range of the current comparator
sense pins is from 0V to (1.1)INTV
CC
. Continuous linear
operation is guaranteed throughout this range allowing
output voltage setting from 0.8V to 7.7V, depending upon
the voltage applied to EXTV
CC
. A differential NPN input
stage is biased with internal resistors from an internal 2.4V
source, as shown in the Functional Diagram. This requires
that current either be sourced or sunk from the SENSE
pins depending on the output voltage. If the output voltage
is below 2.4V, current will flow out of both SENSE pins to
the main output. The output can be easily preloaded by
the V
OUT
resistive divider to compensate for the current
comparators negative input bias current. The maximum
current flowing out of each pair of SENSE pins is:
I
SENSE
+
+ I
SENSE
= (2.4V – V
OUT
)/24k
Figure 6a. Secondary Output Loop and EXTV
CC
Connection Figure 6b. Capacitive Charge Pump for EXTV
CC
EXTV
CC
FCB
SGND
V
IN
TG1
SW
BG1
PGND
LTC3728L/
LTC3728LX
R
SENSE
V
OUT
V
SEC
+
C
OUT
+
1µF
3728 F06a
N-CH
N-CH
R6
+
C
IN
V
IN
T1
1:N
OPTIONAL EXTV
CC
CONNECTION
5V < V
SEC
< 7V
R5
BAT 85
EXTV
CC
V
IN
TG1
SW
BG1
PGND
LTC3728L/
LTC3728LX
R
SENSE
V
OUT
VN2222LL
+
C
OUT
3728 F06b
N-CH
N-CH
+
C
IN
+
1µF
V
IN
L1
BAT85 BAT85
BAT85
0.22µF

LTC3728LEGN#TRPBF

Mfr. #:
Manufacturer:
Analog Devices / Linear Technology
Description:
Switching Voltage Regulators 2x, 550kHz, 2-PhSync Regs
Lifecycle:
New from this manufacturer.
Delivery:
DHL FedEx Ups TNT EMS
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