Obsolete Product(s) - Obsolete Product(s)
L6722 9 Output voltage monitor and protections
25/34
Where V
outMIN
is the UVP threshold, (inductor saturation must be considered). When that
threshold is crossed, all mosfets are turned off, the FAULT pin is driven high and the device
stops working. Cycle the power supply or the INH pin to restart operation.
The maximum average current during the Constant-Current behavior results:
in this particular situation, the switching frequency for each phase results reduced. The ON time
is the maximum allowed T
ON(max)
while the OFF time depends on the application:
The trans-conductance resistor R
ISENx
can be designed considering that the device limits the
bottom of the inductor current ripple and also considering the additional current delivered
during the quasi-constant-current behavior as previously described in the worst case
conditions.
where
Figure 14. Constant current operation
P
EAK
I
OCPx
V
IN
V
OUT min()
L
-------------------------------------------
T
ON max()
+ I
OCPx
V
IN
V
OUT min()
L
-------------------------------------------
0.40 T
S
W
+==
M
AX tot,
3I
MAX
3I
OCPx
I
PEAK
I
OCPx
2
-------------------------------------+
==
T
OFF
L
I
PEAK
I
OCPx
V
OUT
-------------------------------------
= f
1
T
ON max()
T
OF
F
+
--------------------------------------------
--
=
R
ISENx
I
OCPx max()
R
dsON max()
I
OCTH min()
-------------------------------------------------------------------- -= I
OCPx
I
OUT OCP()
3
--------------------------- -
I
PP
2
------------=
V
OUT
0.40 V
IN
Constant Current (Exploded)
I
OCP
= N x I
OCPx
(I
DROOP
= N x 35µA)
I
OUT
UVP Threshold
Resulting Out. Char.
I
MAX,tot
Limted-T
ON
Char.
Droop Effect
Quasi-Const.
Current
T
ON(max)
T
ON(max)
I
OCPx
I
MAX
I
PEAK
LS ON Skipping
Clock Cycles
T
SW
T
SW
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Obsolete Product(s) - Obsolete Product(s)
10 Oscillator L6722
26/34
10 Oscillator
The internal oscillator generates the triangular waveform for the PWM charging and
discharging with a constant current an internal capacitor. The switching frequency for each
channel, F
SW
, is internally fixed at 100kHz so that the resulting switching frequency at the load
side results in being tripled (300kHz).
The current delivered to the oscillator is typically 25µA (corresponding to the free running
frequency F
SW
=100kHz) and it may be varied using an external resistor (R
OSC
) connected
between the OSC pin and SGND. Since the OSC pin is fixed at 1.24V, the frequency is varied
proportionally to the current sunk from the pin considering the internal gain of 4KHz/µA.
In particular connecting R
OSC
to SGND the frequency is increased according to the following
relationship:
R
OSC
vs. SGND
Caution: Maximum programmable switching frequency per phase must be limited to 500kHz to avoid
current reading errors causing, as a consequence, current sharing errors. Anyway, device
power dissipation must be checked prior to design high switching frequency systems.
Figure 15. R
OSC
vs. Switching frequency
F
SW
100kHz
1.240V
R
OSC
k()
--------------------------- -
4
kHz
µA
---------- -
+ 100kHz
4.96 10
6
R
OSC
k()
----------------------------+==
0
50
100
150
200
250
100 150 200 250 300 350 400 450 500 550
Fsw [kHz] Programmed
Rosc [k
Ohms
] to SGND
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L6722 11 System control loop compensation
27/34
11 System control loop compensation
The control loop is composed by the Current Sharing control loop (See Figure 16) and the
Voltage control loop. Each loop gives, with a proper gain, the correction to the PWM in order to
minimize the error in its regulation: the Current Sharing control loop equalize the currents in the
inductors while the Voltage control loop fixes the output voltage equal to the reference.
Figure 16 shows the block diagram of the system control loop.
The system Control Loop is reported in Figure 17. The current information I
DROOP
sourced by
the DROOP pin flows into R
FB
implementing the dependence of the output voltage from the
read current (when DROOP is enabled).
Figure 16. Main control loop
The system can be modeled with an equivalent single phase converter which only difference is
the equivalent inductor L/3 (where each phase has an L inductor).
The Control Loop gain results (obtained opening the loop after the COMP pin):
Where:
is the equivalent output resistance determined by the droop
function;
Z
P
(s) is the impedance resulting by the parallel of the output capacitor (and its ESR) and
the applied load R
O
;
Z
F
(s) is the compensation network impedance;
Z
L
(s) is the parallel of the three inductor impedance;
A(s) is the error amplifier gain;
L3
L2
L1
PWM3
PWM2
PWM1
4 / 5
Reference
ERROR AMPLIFIER
COMP FB
Z
F
(s) Z
F
(s)
I
DROOP
C
OUT
R
OUT
1 / 5
1 / 5
1 / 5
CURRENT SHARING
DUTY CYCLE
CORRECTION
I
INFO1
I
INFO3
I
INFO2
G
LOOP
s()
PWM Z
F
s() R
DROOP
Z
P
s()+()⋅⋅
Z
P
s() Z
L
s()+[]
Z
F
s()
As()
-------------- - 1
1
As()
----------- -+
⎝⎠
⎛⎞
R
FB
+
-----------------------------------------------------------------------------------------------------------------------
--
=
R
DROOP
DCR
Rg
-------------
R
FB
=
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L6722TR

Mfr. #:
Manufacturer:
STMicroelectronics
Description:
Switching Controllers 3 Phase Controller
Lifecycle:
New from this manufacturer.
Delivery:
DHL FedEx Ups TNT EMS
Payment:
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