NCN49599
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25
Figure 25. R
LIM
in Function of the I
LIM
Thermal Protection
Excessive dissipation inside the amplifier, for instance
during overload conditions, can result in damaging junction
temperatures. A thermal shutdown protection monitors the
junction temperature to protect against this.
When the internal junction temperature reaches
approximately 160_C, the amplifier is disabled and placed in
a high−impedance state. The amplifier will be re−enabled
assuming the Enable input is still active − when the junction
temperature cools back down to approximately 135_C.
Safe Operating Area
The safe operating area (SOA) of an amplifier is the
collection of output currents I
L
and the output voltages V
L
that will result in normal operation with risk of destruction
due to overcurrent or overheating.
In a normal application only the output amplifier of the
line driver must be considered; the load on the small−signal
amplifier is usually negligible.
The output amplifier SOA depends on the thermal
resistance from junction to ambient Rth
j−a
, which in turn
strongly depends on board design. Rth
j−a
= 50 K/W in free
air is a typical value, which may be used even if the host
printed circuit board (PCB) is mounted in a small closed
box, provided the transmission of frames are infrequent and
widely spread in time.
This typical value is also used in the generation of the
curves plotted in Figures 26 and 27.
Figure 27 shows the SOA in function of output current I
L
and output voltage V
L
with the ambient temperature as
independent parameter. The maximum allowed current is
800 mA RMS. For that reason it is recommended to limit the
output current by using R
LIM
= 5 kW. This current limitation
is plotted as a horizontal line. The maximal output voltage is
limited by V
CC,max
, V
OH
and V
OL
. This results in the straight
line on the right hand side of the V
L
–I
L
plot. The area below
and left from these limitations is considered as safe. The
relation between output voltage and current is the impedance
as seen at the output of the power operational amplifier.
Constant impedance lines are represented by canted lines.
Figure 26. Example SOA in VLIL space (bottom
left corner is safe) with Rth
j−a
= 50 K/W
Although voltage−versus−current is the normal
representation of safe operating area, a PLC line driver can
only control one of these variables: voltage and current are
linked through the mains impedance. Figure 28 displays
exactly the same information as Figure 27 but might be
easier to work with. Constant current values are now
represented as canted lines.
Figure 27. Example SOA in ZLVL space (bottom
right corner is safe)
Again, the safe operating area depends on PCB layout.
Thus, the designer must verify the performance of her
particular design [1].
Receiver Path Description
The receiver demodulates the signal on the
communication channel. Typically, an external line
coupling circuit is required to filter out the frequencies of
interest on the communication channel.
The receiver block (Figure 29 and Figure 32) filters,
digitalizes and partially demodulates the output signal of the
coupling circuit. Subsequently, the embedded
microcontroller core will demodulate the resulting digital
stream. The demodulation is described in the fact sheets of
the various firmware solutions.
NCN49599
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26
RX_OUT
RX_IN
REF_OUT
LOW NOISE
OPAMP
REF
1,65 V
TO
DIGITAL
Receiver(Analog Path)
Gain LPF
4th
order
SD AD
FROM
DIGITAL
Figure 28. Analogue Path of the Receiver Block
Abs
value
accu
Receiver (Digital Path)
1
st
Decimator
Noise
Shaper
Compen
sator
AGC
Control
FROM
ANALOG
TO
GAIN
f
SI
f
MQ
f
SQ
Sliding
Filter
Sliding
Filter
Sliding
Filter
Sliding
Filter
Quadrature Demodulator
f
S
f
M
2
nd
Decimator
2
nd
Decimator
2
nd
Decimator
2
nd
Decimator
I
M
Q
M
I
S
Q
S
f
MI
FROM TRANSMITTER
f
MQ
f
SI
f
SQ
Figure 29. Digital Path of the Receiver Block
50/60 Hz Suppression Filter
The line coupler − external to the modem and not
described in this document − couples the communication
channel to the low−voltage signal input of the modem.
Ideally the signal produced by the line coupler would only
contain the frequency band used by the S−FSK modulation.
For the common case of communication over an AC power
line, a substantial 50 or 60 Hz residue is still present after the
line coupler. This residue − typically much larger than the
received signal − can easily overload the modem.
To improve communication performance, the NCN49599
provides a low−noise operational amplifier in a unity−gain
configuration which can be used to make a 50/60 Hz
suppression filter with only four external passive
components. Pin RX_IN is the non−inverting input and
RX_OUT is the output of the amplifier.
The internal reference voltage (described below) of
1.65 V is provided on REF_OUT and can be used for this
purpose. The current drawn from this pin should be limited
to 300 mA; in addition, adding a ceramic decoupling
capacitor of at least 1 mF is recommended.
C
1
R
1
C
2
R
2
C
DREF
RX_OUT
RX_IN
REF_OUT
Received
Signal
V
SSA
LOW NOISE
OPAMP
REF
1,65 V
TO AGC
Receiver (S−FSK Demodulator)
V
IN
Figure 30. External Component Connection for 50/60 Hz Suppression Filter
The recommended topology is shown in Figure 20 and
realizes a second order filter. The filter characteristics are
determined by external capacitors and resistors. Typical
values are given in Table 23 for carrier frequencies of 63.3
NCN49599
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27
and 74.5 kHz; the resulting frequency response is shown in
Figure 32. With a good layout, suppressing the residual
mains voltage (50 or 60 Hz) with 60 dB is feasible. To design
a filter for other frequencies, consult the design manual.
T
Frequency (Hz)
10
100 1k 10k 100k
Vin/Vrx_out (dB)
−140
−100
−60
−20
20
Figure 31. Transfer function of the 50 Hz suppression circuit shown in Figure 17
Table 23. VALUE OF THE RESISTORS AND
CAPACITORS
Component Value Unit
C
1
1,5 nF
C
2
1,5 nF
C
DREF
1
mF
R
1
22
kW
R
2
11
kW
It is important to note that the analog part of NCN49599
is referenced to the internal analogue reference voltage
REF_OUT, with a nominal value of 1.65 V. As a result, the
DC voltage on pin RX_IN must be 1.65 V for optimal
dynamic range. If the external signal has a substantially
different reference level capacitive coupling must be used.
Automatic Gain Control (AGC)
In order to extend the range of the analogue−to−digital
convertor, the receiver path contains a variable gain
amplifier. The gain can be changed in 8 steps from 0 to
−42 dB.
This amplifier can be used in an automatic gain control
(AGC) loop. The loop is implemented in digital hardware.
It measures the signal level after analogue−to−digital
conversion. The amplifier gain is changed until the average
digital signal is contained in a window around a percentage
of the full scale. An AGC cycle takes two chip clocks: a
measurement cycle at the rising edge of the CHIP_CLK and
an update cycle starting at the next chip clock.
Low Noise Anti−aliasing Filter and ADC
The receiver has a 3
rd
order continuous time low pass filter
in the signal path. This filter is in fact the same block as in
the transmit path which can be shared because NCN49599
works in half duplex mode. As described in the Low Noise
Anti−aliasing Filter section, the same choice of −3 dB
frequency can be selected between 130 kHz (virtually flat up
to 95 kHz) or 195 kHz (flat up to 148.5 kHz).
The output of the low pass filter is input for an analog 4
th
order sigma−delta converter. The DAC reference levels are
supplied from the reference block. The digital output of the
converter is fed into a noise shaping circuit blocking the
quantization noise from the band of interest, followed by
decimation and a compensation step.
Quadrature Demodulator
The quadrature demodulation block mixes the digital
output of the ADC with the local oscillators. Mixing is done
with the in−phase and quadrature phase of both the f
S
and f
M
carrier frequencies. Thus, four down−mixed (baseband)
signals are obtained.
After low−pass filtering, the in−phase and quadrature
components of each carrier are combined. The resulting two
signals are a measure of the energy at each carrier frequency.
These energy levels are further processed in the firmware.
Communication Controller
The Communication Controller block includes the
micro−processor and its peripherals (refer to Figure 32 for
an overview).

NCN49599MNG

Mfr. #:
Manufacturer:
ON Semiconductor
Description:
Network Controller & Processor ICs 3 DIE MCM CONTAINING PLDA
Lifecycle:
New from this manufacturer.
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